electronic device

专利摘要:
The present invention relates to an electronic device that has a control device, a drive circuit coupled to the control device. The drive circuit is configured to change the conductance. A partial power source is coupled to the control device and is configured to provide a voltage potential difference for the control device and the drive circuit as a result of the partial power source being in contact with a conductive fluid. The partial energy source includes a first material electrically coupled to the control device and a second material electrically coupled to the control device and electrically isolated from the first material. An inductor is coupled to the drive circuit. The drive circuit is configured to develop a current through an inductor. The magnitude of the current developed through the inductor is varied to produce an encoded signal that is remotely detectable by a receiver. Receivers for receiving and decoding are also described.
公开号:BR112019000861B1
申请号:R112019000861-6
申请日:2017-07-24
公开日:2020-10-27
发明作者:Alireza Shirvani；Mark Zdeblick；Jonathan Withrington
申请人:Proteus Digital Health, Inc；
IPC主号:

专利说明:

CROSS REFERENCE TO RELATED ORDERS
[001] This request claims the benefit of US Provisional Order 62 / 365,727, filed on July 22, 2016, and entitled "ELECTROMAGNETIC PERCEPTION AND DETECTION OF INGERIBLE EVENT MARKERS", the description of which is hereby incorporated into your totality and for all purposes. BACKGROUND
[002] The present description is generally related to various devices and techniques for perceiving and detecting an event. More specifically, the present description relates to ingestible identifiers that employ electromagnetic energy to transmit a signal representative of a perception or detection event.
[003] Ingestible event markers that include an electronic circuit have been proposed for use in a variety of different medical applications, including both diagnostic and therapeutic applications. State of the art techniques for detecting an ingestible identifier include making a wet two-point contact on the skin and measuring the difference in tension induced by activating the ingestible identifier. Low signal levels and strong background noise limit these conventional techniques, making the detection and decoding of ingestible identifier signals difficult and computationally intensive. Two other limitations make communication between an ingestible sensor and an external detector unusual. First is that due to the very small amount of energy available in an ingestible sensor and the small size of the ingestible sensor, communication is only one way. There are no acknowledgments returned to the sender, as is typical of virtually all duplex communication systems that are prevalent across the world. Second, due to the small size, a limited list of safe materials that can be ingested, and the very low manufacturing cost required for this application, is not commercially viable - and perhaps not technically viable, but at least it would be extremely difficult - to add a crystal oscillator to the circuit. Thus, an inherent distinguishable characteristic of this communication situation is the uncertainty of the transmitted frequency. While most commercial communication systems operate in an environment where the frequency is known for tens of parts per million, an intake sensor powered by a partial energy source and stomach fluids is challenged to produce a central frequency with a range of + /- 1%. Thus, an important contribution of aspects of the present description is the realization of a communication protocol for RF systems where the transmission power is very low compared to the background noise of the detector and the uncertainty of the transmission frequency is great compared to systems typical modern. Compared to other RF systems, ingestible sensors have an extremely limited size available for both coils that transmit signals and any capacitors that could be used to store energy between communications. Furthermore, the health concerns and opinions of regulatory agencies such as the FDA limit the amount of certain metals that can be digested by a patient, thus putting a cap on the total available energy for both detection and communication. These communication protocols effectively improve the signal levels available for external detection and decoding. There is an incentive to increase the signal levels received from ingestible identifiers so that the ingested identifier can be detected more readily, and by receivers placed over various parts of the body, or used by a patient. SUMMARY
[004] In one aspect, an electronic device is provided. The electronic device comprises a control device, a drive circuit coupled to the control device, a partial power source attached to the control device, the partial power source is configured to provide a voltage potential difference for the control device and the drive circuit as a result of the partial energy source being in contact with a conductive fluid. The partial energy source comprises a first material electrically coupled to the control device and a second material electrically coupled to the control device and electrically isolated from the first material. An inductor is coupled to the drive circuit, where the drive circuit is configured to develop a current through the inductor, and where a magnitude of the current developed through the inductor is varied to produce a coded signal that is remotely detectable by a receiver. .
[005] In another aspect, a receiver circuit is provided. The receiver circuit comprises a resonant circuit, a low noise voltage amplifier coupled to the resonant circuit, and a receiver processor circuit coupled to an output of the low noise voltage amplifier, the receiver processor configured to receive an analog signal. representative of a pulse communication signal, convert the analog signal to a digital signal, and decode the digital signal to reproduce the transmitted data as the pulse communication signal. Furthermore, the receiver is intended for use by a patient on a daily basis for extended periods of time. Therefore, its size and energy consumption are both limited.
[006] In yet another aspect, a receiver circuit is provided. The receiver circuit comprises a reception inductor, a transimpedance amplifier coupled to the receiving coil, an amplifier coupled to an output of the transimpedance amplifier, and a receiver processor circuit coupled to an output of the amplifier, the configured receiver processor to receive an analog signal representative of a pulse communication signal, convert the analog signal to a digital signal, and decode the digital signal to reproduce the transmitted data as the pulse communication signal.
[007] The above is a summary and thus may contain simplifications, generalizations, inclusions and / or omissions of details; consequently, those skilled in the art will appreciate that the summary is illustrative only and is NOT intended to be limiting in any way. Other aspects, characteristics and advantages of the devices and / or processes and / or other subjects described here will be apparent in the teachings presented here.
[008] In one or more aspects, relative systems include, but are not limited to, a circuit and / or programming to carry out the method aspects referenced herein; the circuit and / or programming can be virtually any combination of hardware, software, and / or firmware configured to effect the method aspects referenced here depending on the design choices of the system designer. In addition to the above, several other aspects of method and / or system are presented and described in the teachings such as text (for example, claims and / or detailed description) and / or drawings of the present description.
[009] The above summary is illustrative only and is not intended to be in any way limiting with respect to the scope of the attached claims. In addition to the illustrative aspects and characteristics described above, additional aspects and characteristics will be apparent by reference to the drawings and the following detailed description. FIGURES
[0010] The new characteristics of the aspects described here are presented with particularity in the attached claims. The aspects, however, as far as the organization and methods of operation can be better understood by reference to the following description, taken in conjunction with the accompanying drawings, as follows.
[0011] Figure 1 illustrates a perception and detection system based on an electromagnetic field, according to an aspect of the present description.
[0012] Figure 2 illustrates an individual having swallowed an ingestible identifier, in accordance with an aspect of the present description.
[0013] Figure 3 illustrates a receiver for detecting an electromagnetic field generated by an ingestible identifier, in accordance with an aspect of the present description.
[0014] Figure 4A illustrates a side view of an ingestible identifier comprising an electrically insulating element in accordance with an aspect of the present description.
[0015] Figure 4B illustrates a top view of an ingestible identifier comprising an electrically insulating element in accordance with an aspect of the present description.
[0016] Figure 5 illustrates a block diagram of an aspect of an ingestible identifier with dissimilar metals positioned on opposite ends, according to an aspect of the present description.
[0017] Figure 6 illustrates a block diagram of another aspect of the ingestible identifier with dissimilar metals positioned on the same end and separated by a non-conductive material, according to an aspect of the present description.
[0018] Figure 7 illustrates an ionic transfer or the current path through an electrically conductive fluid when the ingestible identifier of Figure 9 is in contact with a conductive liquid and in an active state, according to an aspect of the present description.
[0019] Figure 7A illustrates an exploded view of the surface of dissimilar materials of Figure 7, in accordance with an aspect of the present description.
[0020] Figure 8 illustrates the ingestible identifier of Figure 5 with a pH sensor unit, according to an aspect of the present description.
[0021] Figure 9 is a block diagram illustration of an aspect of the control device used in the system of Figures 5 and 6, in accordance with an aspect of the present description.
[0022] Figure 10 illustrates a first inductor component, according to an aspect of the present description.
[0023] Figure 11 illustrates a second inductor component, in accordance with an aspect of the present description.
[0024] Figure 12 illustrates an ingestible identifier that includes a conductive communication component and an inductor component, in accordance with an aspect of the present description.
[0025] Figure 13 illustrates a side section view of the ingestible identifier shown in Figure 12, according to an aspect of the present description.
[0026] Figure 14 illustrates an aspect of the ingestible identifier shown in Figures 4A and 4B, according to an aspect of the present description.
[0027] Figure 15 illustrates an aspect of the ingestible identifier shown in Figures 12-13, in accordance with an aspect of the present description.
[0028] Figure 16 illustrates an ingestible identifier comprising an integrated circuit and a separate inductor component formed on a separate substrate, in accordance with an aspect of the present description.
[0029] Figure 17 illustrates an ingestible identifier comprising an inductor formed on a non-conductive membrane, in accordance with an aspect of the present description.
[0030] Figure 18 illustrates an ingestible identifier comprising an inductor formed on one or both of the dissimilar materials shown in Figure 13 after the dissimilar materials are deposited on the integrated circuit, in accordance with an aspect of the present description.
[0031] Figure 19 is a schematic representation of an ingestible identifier comprising an inductor and a single-ended inductor drive circuit, in accordance with an aspect of the present description.
[0032] Figure 20 is a schematic representation of an ingestible identifier comprising an inductor and an inductor drive circuit of the H-type push-pull bridge, in accordance with an aspect of the present description.
[0033] Figure 21 is a schematic representation of an ingestible identifier comprising an inductor and a single-ended inductor drive circuit where a first metallic layer is divided into two regions and the second metallic layer is provided in a single region, of according to one aspect of the present description.
[0034] Figure 21A is a schematic representation of an ingestible identifier comprising an inductor and a single-ended inductor drive circuit where a first metallic layer is divided into two regions and a second metallic layer is divided into two regions, according to with an aspect of the present description.
[0035] Figure 22 is a schematic representation of an ingestible identifier comprising an inductor and a push-pull H type inductor drive circuit where a first metallic layer is divided into two regions and a second metallic layer is provided in a single region, according to one aspect of the present description.
[0036] Figure 22A is a schematic representation of an ingestible identifier comprising an inductor and a H-type push-pull inductor drive circuit where a first metallic layer is divided into two regions and a second metallic layer is divided in two regions, according to one aspect of the present description.
[0037] Figure 23 illustrates an inductive element or inductor structure formed on an insulating substructure, which can be used as the inductive element in an integrated circuit of ingestible identifier, according to an aspect of the present description.
[0038] Figure 24 illustrates an inductive element or multilayer inductor structure formed on an insulating substructure, which can be used as the inductive element in an ingestible identifier integrated circuit, according to an aspect of the present description.
[0039] Figure 25 illustrates a two-port two-layer inductor configuration, in accordance with an aspect of the present description.
[0040] Figure 26 is a two-door two-layer inductor diagram shown in Figure 25, in accordance with an aspect of the present description.
[0041] Figure 27 is a schematic representation of a two-door two-layer inductor shown in Figures 25 and 26, in accordance with an aspect of the present description.
[0042] Figure 28 illustrates a two-port, four-layer inductor configuration in accordance with an aspect of the present description.
[0043] Figure 29 is a four-layer, two-port, 612 inductor diagram shown in Figure 28, in accordance with an aspect of the present description.
[0044] Figure 30 is a schematic representation of the two-door, four-layer inductor shown in Figures 28 and 29, in accordance with an aspect of the present description.
[0045] Figure 31 illustrates a n-layer n-port inductor configuration, in accordance with an aspect of the present description.
[0046] Figure 32 is a n-layer n-port inductor diagram shown in Figure 31, in accordance with an aspect of the present description.
[0047] Figure 33 is a schematic representation of the n-layer n-port inductor shown in Figures 31 and 30, in accordance with an aspect of the present description.
[0048] Figure 34 illustrates a two-layer, three-port symmetrical inductor with a central bypass connection configuration, in accordance with an aspect of the present description.
[0049] Figure 35 is a symmetrical two-port two-layer inductor diagram with a central bypass connection shown in Figure 34, in accordance with an aspect of the present description.
[0050] Figure 36 is a schematic representation of the inductor shown in Figures 34 and 35, in accordance with an aspect of the present description.
[0051] Figure 37 is a schematic diagram of a resonant inductor (oscillatory) drive circuit, according to an aspect of the present description.
[0052] Figure 38 is a block diagram of a pulse inductor drive circuit, according to an aspect of the present description.
[0053] Figure 39 is a schematic diagram of the impulse inductor drive circuit shown in Figure 38, in accordance with an aspect of the present description.
[0054] Figure 40 is a block diagram of the battery voltage duplicating circuit shown in Figures 38 and 39, in accordance with an aspect of the present description.
[0055] Figure 41 is a schematic diagram of each voltage doubling circuit stage shown in Figure 40, in accordance with an aspect of the present description.
[0056] Figure 42 is a schematic diagram of the pulse generator circuit shown in Figures 38 and 39, in accordance with an aspect of the present description.
[0057] Figure 43 is a simplified schematic diagram of an inductor discharge circuit 726 shown in Figures 38 and 39, in accordance with an aspect of the present description.
[0058] Figure 44 is a time and polarity diagram of a pulse communication protocol that can be generated by the pulse inductor drive circuit shown in Figures 38-43, in accordance with an aspect of the present description.
[0059] Figure 45 is a sparse impulse template and autoconvolution diagram of the impulse communication protocol shown in Figure 44, in accordance with an aspect of the present description.
[0060] Figure 46 is a variable template diagram that can be used to identify the transmission frequency of the impulse function shown in Figure 44, in accordance with an aspect of the present description.
[0061] Figure 47 illustrates a voltage mode receiver to detect an electromagnetic field generated by an ingestible identifier, in accordance with an aspect of the present description.
[0062] Figure 48 is a graphical representation of a pulse response from a reception inductor, in accordance with an aspect of the present description.
[0063] Figure 49 illustrates a voltage mode receiver to detect an electromagnetic field generated by an ingestible identifier, in accordance with an aspect of the present description.
[0064] Figure 50 illustrates a current mode receiver, in accordance with an aspect of the present description.
[0065] Figure 51 illustrates another receiver circuit, in accordance with an aspect of the present description.
[0066] Figure 52 illustrates a receiver configuration comprising reception inductors orthogonally spaced with respect to each other and corresponding receivers, in accordance with an aspect of the present description.
[0067] Figure 53 illustrates a receiver configuration comprising orthogonally spaced receiving inductors and corresponding receivers, in accordance with an aspect of the present description.
[0068] Figure 54 illustrates a receiver configuration comprising multiple L1-Ln reception inductors and multiple RXi-RXn receivers, in accordance with an aspect of the present description.
[0069] Figure 55 illustrates a receiver circuit, in accordance with an aspect of the present description.
[0070] Figure 56 is a graph of a pulse transmission spectrum according to an aspect of the present description.
[0071] Figure 57 is a time and polarity diagram of a pulse communication protocol that can be generated by the pulse inductor drive circuit shown in Figures 38-43, in accordance with an aspect of the present description.
[0072] Figure 58 is a time and polarity diagram of a pulse communication protocol that can be received by the receiver circuits shown in Figures 47-53, in accordance with an aspect of the present description.
[0073] Figure 59 is a time and polarity diagram of a pulse communication protocol that can be received by the receiver circuits shown in Figures 47-53, in accordance with an aspect of the present description.
[0074] Figure 60 is a 40-bit packet received by the receiver circuits shown in Figures 47-53, in accordance with an aspect of the present description.
[0075] Figure 61 is a fine spectrum of a packet received by the receiver circuits shown in Figures 47-53, in accordance with an aspect of the present description.
[0076] Figure 62 is a graph showing an example of the "zero" chip pulse sequence, and a graph showing an example of the "one" chip pulse sequence.
[0077] Figure 63 shows a graph of combined data (0 + 1) correlated with one with a template, which illustrates how both frequency and alignment are found: the highest peak determines both.
[0078] Figure 64 shows graphical representations of subchip "A" and subchip "B" in previous graphs.
[0079] Figure 65 is a graph showing how to combine subchips A and B according to the descriptions above produces the chip "Zero" = [A B] and the chip "Um" = [B A].
[0080] Figure 66 is a graph showing how a combined slice can look like SNR = 5000.
[0081] Figure 67 shows a feedback graphic, which is produced by adding the subchip "A" and the subchip "B", and neither decoding is used to find the correct frequency and starting point of the package.
[0082] Figure 68 shows a graph of a typical low-noise convolution for the best matching combination slice; the sum of template convolution versus slice number.
[0083] Figure 69 shows a graph of a spectrum with SNR = 5000, which is a graph of the maximum convolution values for each assumed frequency versus the assumed frequency.
[0084] Figure 70 shows the subchip scores "A" for each slice for the case very low noise: (geometric axis X: slice number, geometric axis Y: correlation value).
[0085] Figure 71 shows an enlarged view at the beginning of the chip score package A: (geometric axis X: slice number, geometric axis Y: correlation to "template A" value).
[0086] Figure 72 shows a graph of both the subchip A and subchip B correlation values together.
[0087] Figure 73 shows a graph of the "zero" chip values as a function of slice number.
[0088] Figure 74 shows a graph of both zero and one chip scores as a function of slice number.
[0089] Figure 75 shows a graph of bit length versus slice number scores.
[0090] Figure 76 shows a graph of a low noise package, with two lines: the line that falls the deepest is the bit length score and the shallowest line is the bit value as interpreted.
[0091] Figure 77 shows four graphs of the combined slice best adjusted in different signal to noise ratios.
[0092] Figure 78 shows several graphs of the "bestThisSums", which is the "best adjusted sums" converted with the "template" for several SNRs.
[0093] Figure 79 shows several spectrum graphs in different SNRs.
[0094] Figure 80 shows the bit length scores used to successfully decode the packet at these various SNR levels.
[0095] Figure 81 shows the first four "A" chips for an additional peak protocol.
[0096] Figure 82 shows a graph of the signal, as transmitted, assuming 240 chips per symbol.
[0097] Figure 83 shows the subchip scores "A" for each slice in case of very low noise.
[0098] Figure 84 shows the F chip scores for each slice in case of very low noise.
[0099] Figure 85 shows a graph of all chip scores A through W versus slice number.
[00100] Figure 86 shows a graph of each of the symbol length versus slice number scores.
[00101] Figure 87 is a graph showing the low noise package (-5.5 dB).
[00102] Figure 88 shows an example of low noise of the correct frequency, which shows a first combined slice of the symbol length slice.
[00103] Figure 89 shows the sum of the second combined slice of the symbol length slice.
[00104] Figure 90 shows two graphs of the same sum of first slice and second slice, in the presence of noise, in the two graphs shown, respectively.
[00105] Figure 91 shows the template used for the symbol length slices.
[00106] Figure 92 illustrates the convolution of the combined slice shown in Graph 2270 with the template shown in Figure 91.
[00107] Figure 93 shows the convolution of the combined slice shown in Graph 2280 with the template shown in Figure 91.
[00108] Figure 94 shows the spectrum: the sum of the magnitudes of the two peaks for each of the symbol length slices as a function of frequency. Figure 95 shows the spectra for both frame length strain / compression analysis and symbol length strain / compression analysis.
[00109] Figure 96 shows the results of a noisier run, where the graph shows the spectrum for the frame length slices as a function of frequency, and the SNR = -13.5 dB.
[00110] Figure 97 shows the spectrum for the frame length slices as a frequency function, where the SNR = -17.5 dB, but with only 120 chips per symbol.
[00111] Figure 98 is the same 2-slice, same data set as in graph 2280 (see Figure 90), but at a frequency that is 10 units higher.
[00112] Figure 99 shows the second slice of the symbol length slice, with SNR = 7 dB, but the frequency is in 551 units instead of 501.
[00113] Figure 100 shows a graph of the raw frequency spectrum for the sensor emulator 228.6 mm (9 inches) from the detector.
[00114] Figure 101 shows a graph of the fine frequency spectrum for the sensor emulator 228.6 mm (9 inches) from the detector.
[00115] Figure 102 shows a graph of the combined frame length slice of the detector at 228.6 mm (9 inches) from the source.
[00116] Figure 103 is a graph showing BestSums using data gathered 228.6 mm (9 inches) from the source.
[00117] Figure 104 is a graph showing the symbols of package and forces using data gathered 228.6 mm (9 inches) from the source.
[00118] Figure 105 is a graph showing the raw frequency spectrum for the sensor emulator 609.6 mm (24 inches) from the detector.
[00119] Figure 106 shows the fine frequency spectrum P3SS2 for sensor emulator 609.6 mm (24 inches) from the detector.
[00120] Figure 107 shows the thin full frame frequency spectrum for the sensor emulator at 609.6 mm (24 inches) from the detector.
[00121] Figure 108 shows a graph of the best combined total frame slice along with the best fit template for a signal received 609.6 mm (24 inches) from the source.
[00122] Figure 109 is a graph showing the result of bestSums (result of template convolution with combined slice) for data gathered 609.6 mm (24 inches) from the source.
[00123] Figure 110 is a graph showing the symbol and package result values for data gathered 609.6 mm (24 inches) from the source.
[00124] Figure 111 is a graph showing BestSums using data gathered at 609.6 mm (24 inches) from the source. DETAILED DESCRIPTION
[00125] In the following detailed description reference is made to the drawings which form a part thereof. In the drawings, similar symbols and reference characters typically identify similar components across all the different views, unless the context dictates otherwise. The illustrative aspects described in the detailed description, drawings, and claims are not intended to be limiting. Other aspects can be used, and other changes can be made, without departing from the spirit or scope of the subject presented here.
[00126] Before explaining the various aspects of perceiving and detecting ingestible identifiers using electromagnetic signals in detail, it should be noted that the various aspects described here are not limited in their application or use to the details of construction and arrangement of parts illustrated in the accompanying drawings and description. Instead, the aspects described can be positioned or incorporated into other aspects, their variations and modifications, and can be practiced or executed in several ways. Consequently, aspects of perception and detection intake identifiers that use electromagnetic signals described here are illustrative in nature and are not intended to limit its scope or application. Furthermore, unless otherwise indicated, the terms and expressions used herein have been chosen for the purpose of describing the aspects for the reader's convenience and should not limit their scope. Furthermore, it should be understood that any one or more of the described aspects, expressions of aspects and / or their examples, can be combined with any one or more of the other described aspects, expressions of aspects, and / or their examples, without limitation.
[00127] Also in the following description, it should be understood that terms such as front, back, inside, outside, top, bottom and the like are words of convenience and should not be considered as limiting terms. The terminology used here is not intended to be limiting to the extent that the devices described herein, or their portions, can be attached or used in other orientations. The various aspects will be described in more detail with reference to the drawings.
[00128] As previously described, conventional means of detecting an ingestible identifier include making wet contact with two points of the skin and measuring the voltage difference induced by conductive electrical currents that flow through the patient's body after activating the ingestible identifier. Weak weak signal levels and strong background noise can limit the conductive current technique and can make the detection and decoding of ingestible identifier signals difficult and computationally intensive. Furthermore, in conventional perception and detection techniques, the signal weakens as the receiver is moved away from the abdomen to locations such as the neck, chest or chest, arm, wrist, thigh or leg, for example. GENERAL VIEW
[00129] In several aspects, an electromagnetic coil in the form of an electrical conductor such as a wire in the form of a coil, spiral or helix can be used to generate electromagnetic signals. The electric currents generated in electromagnetic coils interact with magnetic fields in devices such as inductors and sensor coils. Either an electric current is passed through the coil wire to generate a magnetic field, or on the contrary, an external time-varying magnetic field through the interior of the coil generates an EMF (voltage) in the conductor. As described in more detail below, an electromagnetic signal can be generated by an inductor formed on a semiconductor substrate comprising active device regions. Conductive inductive elements can be formed on a dielectric layer superimposed on a semiconductor substrate or a glass substrate, for example. Conductive elements can be patterned and engraved in a desired shape such as a flat spiral, for example. A substrate region below the inductor can be removed to decrease the inductive Q factor. The current revolution in wireless communications and the need for smaller wireless communications devices have sparked significant efforts aimed at optimizing and miniaturizing electronic radio communications devices. Passive components (such as inductors, capacitors and transformers) play a necessary role in the operation of these devices and thus efforts have been directed towards reducing the size and improving the performance and manufacturing efficiency of such passive components.
[00130] Discrete inductors and capacitors are passive electromagnetic components used in alternating current and radio frequency applications, such as oscillators, amplifiers and signal filters, to provide frequency-dependent effects. Specifically, the voltage across the inductor is a function of the product of the inductance and the time derivative of the current through the inductor. A conventional inductor comprises a plurality of windings that surround a core constructed of a ferromagnetic or insulating material. Although an inductor core is not required, the use of a ferromagnetic core, for example, increases the inductance value. Inductance is also a function of the number of coil turns (specifically, the inductance is proportional to the square of the number of turns) and the core area. Conventional discrete inductors are formed as a helix (also referred to as a solenoid shape) or a toroid. The core is typically formed of iron, cobalt or nickel (or a ferromagnetic alloy) that comprises a plurality of magnetic domains. The current supplied to the inductor induces a magnetic field in the core material, causing a domain alignment and a resulting increase in the permeability of the material, which, in turn, increases the inductance.
[00131] Developments in the semiconductor industry have over the years been directed towards manufacturing higher performance devices of decreasing size. A challenge in semiconductor circuit design and fabrication is the integration of high performance capacitors and inductors in the semiconductor device. Ideally, these components are formed over a relatively small surface area of a semiconductor substrate, using methods and procedures that are conventional in the semiconductor fabrication technique. However, compared to the characteristic sizes and line widths of active devices, the inductors and capacitors are large and not easily integrated into semiconductor devices that typically have characteristic sizes in the submicron range. It will be appreciated that inductors can be formed on a glass substrate instead of a semiconductor substrate, for example.
[00132] Most inductors formed on a semiconductor or glass substrate surface have a spiral shape, where the plane of the spiral is parallel to the substrate surface. Many techniques are known to form a spiral inductor, such as masking, patterning, and etching a layer of conductive material formed on the substrate surface. Multiple interconnected spiral inductors can also be formed to provide the desired inductive properties and / or to simplify the manufacturing process. See, for example, US Patent Number 6,429,504, which describes a multilayer spiral inductor and US Patent Number 5,610,433, which describes a high value inductor with a high Q factor formed from a plurality of layers with each layer comprising two or more. The coils in the various layers are interconnected in series so that the current flows through the inductors in the same direction, for example.
[00133] The Q (or quality factor), an important figure of merit for an important inductor is defined as the ratio of inductive reactance to resistance. High Q inductors (for example, which have a low resistance) exhibit a narrow Q peak as a function of the input signal frequency, where the peak occurs at the inductor resonant frequency. High Q inductors are especially important for use in frequency-dependent circuits that operate with narrow bandwidths. For example, increasing the Q for an inductor that operates on an oscillator decreases the oscillator phase noise, and confines the oscillator frequency to a narrower frequency band. Since the Q value is an inverse function of inductor resistance, minimizing resistance increases Q. A known technique for minimizing resistance increases the cross-sectional area of the conductive material that forms the inductor.
[00134] Several aspects of the present description leverage alternative physical phenomena for conventional conductive current based on ingestible identifier detection techniques. In one aspect, for example, the present description provides techniques for the perception and detection of ingestible identifiers that employ the generation of electromagnetic fields by the electric currents induced in the stomach fluid by the ingestible identifier, which move more readily within and on the body surface. . A receiving device, namely an antenna, such as an inductor, can be used to receive the electromagnetic field and convert it to a voltage. Such voltage can then be received by any suitable means, such as discrete or integrated electronics. See Wang, Jianqing, Qiong Wang, Body Area Communications: Channel Modeling, Communication Systems, and EMC. Singapore: John Wiley & Sons Singapore Pte. Ltd., 2013, for example, for a discussion of body area communication techniques.
[00135] For directionality, so that the electromagnetic field receiver does not pick up signals from adjacent patients, a magnetic shield can be placed on top of the receiving antenna (for example, inductor). By confining the antenna between the shield and the body, the receiver will only receive fields that move within the body. As an improvement, the shield can be made as a parabolic surface, with the antenna (inductor) placed at the focal point to improve the signal strength as is done in satellite dish antennas.
[00136] Figure 1 illustrates an electromagnetic field based on a perception and detection system 100, in accordance with an aspect of the present description. Figure 1 shows an individual 102 who recently swallowed an ingestible identifier 104. Ingestible identifier 104, as described in more detail below, generates an encoded electromagnetic signal when it comes into contact with gastrointestinal fluids within the individual's stomach 102. Although the encoded electromagnetic signal can be configured to represent many variables, in one aspect, the encoded electromagnetic signal represents an ingestible event. In one aspect, an ingestible event may be associated with individual 102 taking medication dosage, type of medication, or dosage amount, or their combinations, among other variables.
[00137] The implementation of system 100 can include many variations. For example, in one aspect, an ingestible identifier, as described in connection with Figures 4-9, can be employed. In this implementation, the ingestible identifier is energized when it comes in contact with an electrically conductive fluid and then generates an electromagnetic field that can be detected by an inductor antenna, for example. This technique is advantageous because an electromagnetic field tends to propagate better over a patient's skin surface compared to conducting an electric current over the skin's surface. The electromagnetic field on the skin surface can be derived with an inductor antenna that has N windings, where N is an integer, and optionally a ferrite core to increase sensitivity. As the body of the individual 102, aids the propagation of the electromagnetic field, the system 100 provides additional flexibility in locating and placing the inducer antenna of the ingestible identifier 104 and / or the receiver 106, 108, 110, 112, 114, 116, 118, 150, 152, for example.
[00138] In another aspect, the ingestible identifier can include an amplifier to amplify the signal generated by the ingestible identifier circuit. The inductor winding can be provided over the same integrated circuit as the ingestible identifier. In another aspect, the inductor windings can be printed on a non-conductive membrane interposed between the electrodes made of dissimilar materials located on the ingestible identifier (for example, a skirt). In some aspects, the inductor antenna can be printed using a conductive digestible material or on the non-conductive membrane or integrated circuit. In another aspect, an inductor winding can be added as a separate integrated circuit and coupled to the ingestible identifier circuit. Furthermore, the system 100 can operate at various frequencies, such as, for example, 100 kHz to 1 MHz, which can provide opportunities to reduce the size of the transmitter inductor and the receiver inductor antenna. The upper frequency limit can be detected by the limit at which the individual's body 102 begins to absorb electromagnetic energy. Such an upper frequency limit can be approximately 400 MHz, without limitation. In other implementations, the operating frequency can be selected from 10 Mhz to 1 GHz, for example.
[00139] In several aspects, an inductor that has N turns can be positioned on two sides of the ingestible identifier integrated circuit. The excitation would be positive on one side and negative on the other side to increase or double the signal strength. The ingestible identifier can be configured to transmit on multiple frequencies, instead of a single frequency, by adding multiple transmitters and multiple inductors, or a single transmitter coupled to multiple inductors through a multiplexer, or a single transmitter and single inductor coupled to multiple tuning elements, such as two or more capacitors, through a multiplexer. In other respects, magnetic materials, such as a ferrite inductor, for example, can be deposited or added to the ingestible identifier integrated circuit to increase the inductance of the transmission inductor. In other respects, the ingestible identifier electrodes can be formed in the form of an inductor.
[00140] In other aspects, the ingestible identifier may be configured to communicate directly with a mobile telecommunication device, such as a mobile phone, cell phone, or smartphone provided with increased signal strength availability and data security consideration.
[00141] The electromagnetic signal page 17 emitted by the ingestible identifier 104 can be detected by a receiver associated with individual 102. In several aspects, the ingestible identifier 104 and any of the receivers 106, 108, 110, 112, 114, 116, 118 , 150, 152 can be configured for one-way, and in some cases, two-way communication. Receptors 106, 108, 110, 112, 114, 116, 118, 150, 152 can be configured to perceive and detect ingestible identifier 104 and can be located on or outside the body of the individual 102. Thus, receptors 106, 108 , 110, 112, 114, 116, 118, 150, 152 can be located on the body of individual 102, partially or fully implanted in individual 102, or they can be located outside of individual 102 but close to individual 102 so that a receiver can readily detect a relatively weak electromagnetic signal.
[00142] In one aspect, a receptor 106 may be located on a bandage and adhered to the abdomen of the individual 102 or anywhere on the lower body of the individual 102 to perceive and detect the ingestible identifier 104 after the ingestible identifier is ingested by the individual 102 In another aspect, a recipient 108 may be located on a bandage and adhered to the individual's chest, chest, or upper body portions 102. In yet another aspect, a recipient 116 may be located on a bandage or necklace and used close to or around the neck or throat, or another location on or near the head, of individual 102. In another aspect, a receiver 110 can be located in an arm band and used around the upper arm of individual 102 near the shoulder, for example example. In another aspect, a receiver 112 may be located on a watch and worn around the wrist of individual 102. In yet another aspect, a receiver 152 may be located on a wrist band and worn around the wrist of individual 102. In in yet another aspect, a receiver 150 may be located on a belt and worn around the waist of individual 102. In yet another aspect, a receiver 114 may be located on an ankle band and worn around the ankle of individual 102 or other locations on individual 102's leg. In several other respects, a receiver may be located anywhere on or near individual 102. In another aspect, a receiver 118 may be located outside the body, but closer to individual 102. For For example, the receiver 118 may be located inside the pocket 120 of a garment 122 worn by the individual 102.
[00143] Receivers 106, 108, 116 which are directly coupled to the body of individual 102, can be attached by an adhesive applied to the skin contact surface of receiver 106, 108, 116. Receivers 110, 112, 152 that are placed around the subject's arm or wrist may include a band or tape to hold the receiver 110, 112, 152 in place. In one aspect, the receiver 112 may have a shape factor similar to a wristwatch. Receiver 118 may be loosely positioned inside pocket 120 of clothing 122 worn by individual 102. Receiver 150 may be worn around the waist like a belt.
[00144] In present implementations of systems for perceiving and detecting identifiable ingestable low-energy electromagnetic signals may be required to limit the spread of the field beyond the individual's body 102 to maintain the privacy of the information carried by the electromagnetic signals.
[00145] In several respects, an electromagnetic shield or "jacket" can be positioned over the receiver inductor antenna to shield the receiver from electromagnetic waves from sources external to the individual's body 102. In some respects, the shield can be formed as a parabolic reflector to focus the electromagnetic field of the individual's body into the receiver inductor antenna. In other respects, two inductors can be positioned in a perpendicular or orthogonal orientation with respect to each other over the ingestible identifier to provide a more inhomogeneous reception of the electromagnetic signal. Other forms of antennas such as dipole or bandage antennas can be employed in the receiver technique in addition to the inducing antenna.
[00146] Figure 2 illustrates an individual 102 who swallowed an ingestible identifier 104, in accordance with an aspect of the present description. When ingestible identifier 104 is immersed in electrolytic fluids typically found within stomach 132, an internal partial battery is activated to energize the electrical circuits of ingestible identifier 104. As shown, ingestible identifier 104 is transmitting an electromagnetic field 136 within body 130 of the individual 102. The ingestible identifier 104 includes an inductor in a resonant circuit to adjust the frequency of the electromagnetic field 136. The electromagnetic field 136 propagates through the entire body 134 and propagates over the surface of the body 130 where it can be detected by a receiver 106 located close to the abdomen of the body 130. The receiver 106 comprises an inductor antenna for detecting the electromagnetic field 134. The ingestible identifier 104 includes a circuit to encode the electromagnetic field 134 with information programmed in the ingestible identifier 104.
[00147] Figure 3 illustrates a receiver 106 for detecting an electromagnetic field generated by an ingestible identifier, in accordance with an aspect of the present description, such as ingestible identifier 104 discussed in connection with Figures 1 and 2. Receiver 106 comprises a resonant circuit 140 and receiver electronics 142 for processing the encoded electromagnetic signal received from the ingestible identifier. The resonant circuit 140 may comprise an inductor antenna 144 and a tuning capacitor 146 for resonating at the operating frequency. TRANSMISSION BY INGERIBLE IDENTIFIER
[00148] Figures 4A and 4B illustrate several views of an ingestible identifier 200 comprising an electrically insulating element 208, in accordance with an aspect of the present description. The electrically insulating element 208 extends beyond the outer edges of integrated circuit 202. Figure 4B is a plan view of the identifier 200 shown in Figure 4A. As shown in Figure 4A, integrated circuit 202 comprises an upper electrode 204 composed of a first material and a lower electrode 206 composed of a second material, where the first and second materials are dissimilar and have a different electrochemical potential. As shown in Figure 4B, the electrically insulating element 208 has a disk shape. With reference to Figures 4A and 4B, the upper and lower electrodes 204, 206 and integrated circuit 202 are positioned within or near the center of the disc-shaped electrically insulating element 208. The distance from the edge of the electrically insulating element 208 to the perimeter of integrated circuit 202 and electrodes 204, 206 may vary, and certain aspects are ~ 0.05 mm or more, for example, ~ 0.1 mm or more, including ~ 1.0 mm or more, such as ~ 5, 0 mm or more and including ~ 10 mm or more, where the distance may not exceed ~ 100 mm in certain respects. An inductor or inductive elements can be arranged on the electrically insulating element 208, taking advantage of the greater surface area available in relation to the surface area available on the integrated circuit 202.
[00149] In the example shown in Figures 4A to 4B, the upper and lower electrodes 204, 206 have a flat configuration. In other respects, however, electrodes 204, 206 may have any convenient shape, for example, square, disc, etc., flat or otherwise. The disk-shaped electrically insulating element 208 has a flat disk structure, where the edge of the electrically insulating element 208 extends beyond the edge of the flat top and bottom electrodes 204, 206 and integrated circuit 202. In the example shown, the radius of the electrically insulating element 208 is greater than the radius of the upper and lower electrodes 204, 206, for example, by ~ 1 mm or more, such as by ~ 10 mm or more.
[00150] It is noted that in any given example, the electrically insulating element 208 may or may not extend beyond the edge of electrodes 204, 206 or integrated circuit 202. For example, as shown in Figures 4A to 4B, the electrically insulating element 208 extends beyond the edge of the upper and lower electrodes 204, 206 as well as the integrated circuit. However, in other examples, the electrically insulating element 208 may define an edge proportional to the edge of one of the electrodes, for example, the lower electrode 206, so that it does not extend beyond the edge of both electrodes 204, 206 or the integrated circuit 202, where the electrically insulating element 208 may include an edge that extends beyond the edge of the upper electrode 204, but not beyond the edge of the lower electrode 206.
[00151] Figures 5-9 illustrate various aspects of ingestible identifier systems 210, 220, 260 in accordance with various aspects of the present description. The ingestible identifier systems 210, 220, 260 shown in Figures 5-9 comprise a solid state semiconductor switch 400 coupled to a 401 inductor. The solid state semiconductor switch 400 switches power (AC or DC current) to the inductor 401 under the control of an electronic control device 218 (Figures 5, 7, 8), 228 (Figure 6). It will be appreciated that Figures 5-8 are for simplified block diagram circuits and are intended for illustrative purposes only. Consequently, the solid state semiconductor switch 400 and / or inductor 401 may include additional circuits or subcircuits.
[00152] With reference to Figures 5 and 7, the ingestible identifier system 210 comprises a first material 214 (metal 1) and a second material 216 (metal 2) applied to the frame 212 of a control device 218. The output of the device control 218 is coupled to the solid state semiconductor switch 400 which controls the current flow through inductor 401 to generate an electromagnetic field. This configuration provides a battery created by the first material 214 (metal 1) and the second material 216 (metal 2) when exposed to an ionic solution. Thus, when system 210 is in contact with and / or partially in contact with an electrically conductive liquid, a current path 230, 250, as shown in Figure 7 by way of example, is formed through the conductive liquid between the first and according to dissimilar materials 214, 216. The battery activates the control device 218, which creates an oscillating frequency controlling the switched current inside inductor 401. The oscillating current flows through inductor 401 when switch 400 is closed and generates an electromagnetic signal RF. The electromagnetic RF signal is propagated through the individual's body and can be detected by an external or internal receiver device that has an electromagnetic signal detection mechanism. If a transmission is provided at a high enough energy, a device like a pager that is used by the patient will detect whenever a pill is ingested.
[00153] With reference to Figure 5, the first and second dissimilar materials 214, 216 (metal 1 and metal 2) are positioned on their opposite ends. The ingestible identifier system 210 can be used in combination with any pharmaceutical product, as mentioned above, to determine when a patient takes the pharmaceutical product. As indicated above, the scope of the present description is not limited by the environment and the product that is used with the 210 system. For example, the 210 system can be placed inside a capsule and the capsule is placed inside the conductive liquid. The capsule would then dissolve over a period of time and release system 210 into the conductive liquid. Thus, in one aspect, the capsule would contain system 210 and no product. Such a capsule can then be used in any environment where an electrically conductive liquid is present and with any product. For example, the capsule can be dropped into a container filled with jet fuel, salt water, tomato juice, motor oil or any similar product. Furthermore, the capsule containing system 210 can be ingested at the same time that any pharmaceutical product is ingested in order to record the occurrence of the event, such as when the product was taken.
[00154] In the specific example of system 210 shown in Figure 5 combined with a pharmaceutical product, as the product or pill is ingested, system 210 is activated. In one aspect, system 210 generates an electromagnetic signal controlling the current driven into inductor 401 by the control device 400 to produce a single electromagnetic signal that is detectable with receivers described herein, thereby meaning that the pharmaceutical product has been taken. Structure 212 is a chassis for system 210 and multiple components are attached to, deposited on, or attached to structure 212. In this aspect of system 210, a first digestible material 214 is physically associated with the structure. 212. The first material 214 can be chemically deposited on, evaporated on, trapped in, or accumulated on the structure all of which can be referred to here as "deposit" with respect to structure 212. The first material 214 is deposited on one side of the structure 212. Materials of interest that can be used as the first material 214 include, but are not limited to: Cu or CuCI. The first material 214 is deposited by physical vapor deposition, electrodeposition, or plasma deposition, among other protocols. The first material 214 can be approximately ~ 0.05 to approximately ~ 500 pm in thickness, such as approximately ~ 5 to approximately ~ 100 pm in thickness. The shape is controlled by deposition of shade mask, or photo lithography and engraving. Furthermore, although only one region is shown to deposit the material, each of the systems 210 can contain two or more electrically unique regions where material 214 can be deposited, as desired.
[00155] On a different side, which is the opposite side as shown in Figure 5, another second, digestible material 216 is deposited, so that the first and second materials 214, 216 are dissimilar. Although not shown, the different side selected may be the side next to the side selected for the first material 214. The scope of this description is not limited by the side selected and the term "different side" can mean any of the multiple sides that are different from the first selected side. Furthermore, although the shape of the system is shown as a square, the shape can be any geometrically suitable shape. The first and second dissimilar materials 214, 216 are selected so that they produce a voltage potential difference when the system 210 is in contact with an electrically conductive liquid, such as body fluids. Materials of interest for material 216 include, but are not limited to: Mg, Zn, or other electronegative metals. As indicated above with respect to the first material 214, the second material 216 can be chemically deposited on, evaporated on, trapped in, or accumulated on the structure. Also, an adhesion layer may be required to assist the second material 216 (as well as the first material 214 when necessary) to adhere to structure 212. Typical adhesion layers for material 216 are Ti, TiW, Cr or a similar material. The anode material and the adhesion layer can be deposited by physical vapor deposition, electrodeposition or plasma deposition. The second material 216 can be approximately ~ 0.05 to approximately ~ 500 pm in thickness, such as approximately ~ 5 to approximately ~ 100 pm in thickness. The scope of this description, however, is not limited by the thickness of any of the materials or the type of process used to deposit or secure the materials in the 212 structure.
[00156] Thus, when the system 210 is in contact with an electrically conductive liquid, a current path, an example is shown in Figure 7, is formed through the conductive liquid between the first and second materials 214, 216. The control 218 is attached to structure 212 and electrically coupled to the first and second materials 214, 216. The control device 218 includes an electronic circuit, for example, control logic that is able to control and change the conductance between the first and second materials 214, 216 as well as an electronic circuit to drive a current through inductor 401 to generate a unique electromagnetic signal that is encoded to provide a unique identifier that corresponds to system 210 and / or the product that system 210 is attached or combined with.
[00157] The voltage potential created between the first and second materials 214, 216 provides the energy to operate system 210 including control device 218 and inductor 401. In one aspect, system 210 operates in direct current mode ( CC). In an alternative aspect, system 210 controls the direction of the current so that the current direction is reversed in a cyclic mode, similar to the alternating current (AC) mode. As the system reaches the electrically conductive fluid or electrolyte, where the fluid or electrolyte component is provided with a physiological fluid, for example, stomach acid, the path for current flow between the first and second materials 214, 216 is completed externally system 210; the current path through system 210 is controlled by control device 218. Completing the current path allows current to flow and a receiver, not shown, can detect the presence of current and recognize that system 210 has been activated and the desired event is occurring or has occurred.
[00158] In one aspect, the two materials 214, 216 are similar in function to the two electrodes needed for a direct current (DC) power source, such as a battery. The electrically conductive liquid acts as the electrolyte needed to complete the energy source. The completed energy source described is defined by the physical chemical reaction between the first and second materials 214, 216 of system 210 and the fluids surrounding the body. The completed energy source can be seen as an energy source that exploits reverse electrolysis in an ionic or conductive solution such as gastric fluid, blood, or other body fluids and some tissues. Furthermore, the environment can be something other than a body and the liquid can be any conductive liquid. For example, the electrically conductive fluid can be salt water or a metal-based paint.
[00159] In certain respects, the two materials 214, 216 can be shielded from the surrounding environment by an additional layer of material. Consequently, when the shield is dissolved and the two dissimilar materials are exposed to the target site, a voltage potential is generated.
[00160] Referring further to Figure 5, the first and second materials 214, 216 provide the voltage potential to activate the control device 218. Once the control device 218 is activated or switched on, the control device 219 can change conductance through inductor 401 in a single mode to produce a single electromagnetic signal. By changing the current flow through inductor 401, the control device 218 is configured to control the magnitude, phase, or direction of the current through inductor 401. This produces a unique electromagnetic signature that can be detected and measured by a receiver (not shown), which can be positioned internal, external, partially internal, or partially external to a patient's body.
[00161] Furthermore, the electrically insulating elements 215, 217 can be arranged between the first and second materials 214, 216 and can be associated with, for example, fastened to structure 212. Various shapes and configurations for the electrically insulating elements 215 , 217 are considered to be within the scope of this description. For example, the system 210 may be surrounded entirely or partially by the electrically insulating elements 215, 217 and the electrically insulating elements 215, 217 may be positioned along a central axis of the system 210 or off center in relation to a geometric axis central. Thus, the scope of the present description as claimed herein is not limited by the shape or size of the non-conductive membrane 215, 217. Furthermore, in other respects, the first and second dissimilar materials 214, 216 can be separated by a membrane that is positioned in any region defined between the first and second materials 214, 216.
[00162] In several respects, inductor 401 may include a predetermined number of windings and may be an integrated circuit with frame 212 or control device 218. Inductor windings 401 may be formed either on the substrate of structure 212 or the control device 218 can be printed on the electrically insulating elements 215, 217 interposed between the first and second materials 214, 216 located on the ingestible identifier 210. In some aspects, the inductor 401 can be printed using a conductive digestible material or on the electrically insulating elements 215, 217 or on the integrated control device 218. In another aspect, an inductor winding can be added as a separate integrated circuit coupled to the ingestible identifier control device 218.
[00163] The conductive current generated by the ingestible identifier 210 can be routed through inductor 401 by switch 400 via a switch or switching matrix, as shown in Figures 21, 21A showing a single end inductor arrangement 420 and circuit drive 500 and Figures 22, 22A showing a push-pull H-bridge inductor arrangement 504 and a drive circuit 502, for example. Referring back to Figure 5, system 210 may be configured to operate at various frequencies such as, for example, approximately 100 kHz to approximately 1 MHz, which may provide opportunities to reduce the size of the transmitter inductor and the antenna of receptor inducer. The upper frequency limit can be detected by the limit at which the individual's body 102 (Figure 1) begins to absorb electromagnetic energy. Such an upper frequency limit can be approximately 400 MHz, without limitation.
[00164] Figure 6 shows an ingestible identifier 220 comprising a first material 224 (metal 1) and a second material 226 (metal 2) applied to the frame 222 of an electronic control device 228. The output of the control device 228 is coupled to the solid state semiconductor switch 400 which controls the current flow through inductor 401 to generate an electromagnetic field. This configuration provides a battery created by the first material 224 (metal 1) and the second material 226 (metal 2) when exposed to an ionic solution. The battery drives the control device 228, which creates an oscillating frequency by controlling the switched current into inductor 401. The oscillating current flows through inductor 401 when switch 400 is closed and generates an electromagnetic RF signal. The electromagnetic RF signal is propagated through the individual's body and can be detected by an external or internal receiver device that has an electromagnetic signal detection mechanism. If a transmission is provided at a high enough energy, a device like a pager that is used by the patient will detect whenever a pill is ingested.
[00165] Structure 222 of system 220 shown in Figure 6 is similar to structure 212 of system 210 shown in Figure 5. In this aspect of system 220, a digestible or dissolvable material 224 is deposited on a portion on one side of structure 222. In a different portion on the same side of structure 222, another digestible or dissolvable material 226 is deposited, so that the two materials 224, 226 are dissimilar. More specifically, the first and second materials 224, 226 are selected so that they generate a voltage potential difference when in contact with an electrically conductive liquid, such as body fluids.
[00166] Control device 228 is attached to structure 222 and electrically coupled to dissimilar materials 224, 226. Control device 228 includes an electronic circuit that is capable of controlling part of the conductance path between materials 224, 226 Materials dissimilar elements 224, 226 are separated by a non-conductive (electrically insulating) element 229. Several examples of electrically insulating element 229 are described in US Patent No. 8,545,402, filed April 27, 2010 and entitled "HIGHLY RELIABLE EVENT MARKERS" AND METHODS FOR USING THE SAME "and US Patent Number 8,961,412 filed on September 25, 2008 entitled" BODY DEVICE WITH AMPLIFICATION OF VIRTUAL DIPOLO SIGNAL "; the entire description of each is incorporated by reference.
[00167] Once the control device 228 is activated or switched on, the control device 228 can change the conductance between dissimilar materials 224, 226. Thus, the control device 228 is able to control the magnitude of the current through the electrically conductive liquid surrounding system 220. As noted above with respect to system 210, a single current signature that is associated with system 220 can be detected by a receiver (not shown) to mark activation of system 220. So increasing the "length" of the current path the size of the electrically insulating membrane 229 is changed. The longer the current path, the easier it can be for the receiver to detect the current.
[00168] In several respects, as described in more detail below, system 220 may comprise a transmission inductor 401 to generate an electromagnetic field. The inductor 401 can include a predetermined number of windings and can be integrated with the control device 228 of the ingestible identifier 210. In another aspect, the inductor windings can be printed on the electrically insulating membrane 229 interposed between the electrodes 224, 226. Inductor 401 can be printed using a digestible conductive material or electrically insulating membrane 229 or can be integrated with control device 228. In another aspect, an inductor winding can be added as a separate integrated circuit coupled to the control device of ingestible identifier 228. The conductive current generated by ingestible identifier 220 can be routed through inductor 401 by switch 400 before the current is routed to the battery circuit of system 220. System 220 can be configured to operate at various frequencies, such as for example, approximately 100 kHz to approximately 1 MHz, which can provide opportunities to reduce the size of the 401 transmitter inductor and the receiver inductor antenna. The upper frequency limit can be detected by the limit at which the individual's body 102 (Figure 1) begins to absorb electromagnetic energy. Such an upper frequency limit can be approximately 400 MHz, without limitation.
[00169] Figure 7 illustrates the system 210 shown in Figure 5 in an activated state and in contact with an electrically conductive liquid, according to an aspect of the present description. System 210 is grounded via a ground contact 232. System 210 also includes a sensor component 254, which is described in more detail with reference to Figure 9. Ion or current paths 230 are established between the first material 214 and the second material 216 through the electrically conductive fluid in contact with the system 210. The stress potential created between the first and the second dissimilar materials 214, 216 is created through chemical reactions between the first and the second dissimilar materials 214, 216 and the electrically conductive fluid.
[00170] Figure 7A shows an exploded view of the surface of the first material 214, according to an aspect of the present description. The surface of the first material 214 is not flat, but instead has an uneven surface 234 as shown. The uneven surface 234 increases the surface area of the material and, thereby, the area that comes into contact with the electrically conductive fluid. It will be appreciated that the second material 216 shown in Figure 7 can also have an uneven surface.
[00171] In one aspect, on the surface of the first material 214, there is a chemical reaction between the first material and the surrounding electrically conductive fluid so that a mass is released into the electrically conductive fluid. The term "mass" as used herein refers to protons and neutrons that form a substance. An example includes the time when the material is CuCI and when in contact with the electrically conductive fluid, CuCI becomes Cu (solid) and Cl- in solution. The flow of ions into the conduction fluid is shown by ion paths 230. In a similar way, there is a chemical reaction between the second material 216 and the surrounding electrically conductive fluid and ions are captured by the second material 216. The release of ions in the first material 214 and the capture of ions by the second material 216 is collectively referred to as ion exchange. The ion exchange rate, and thus the ion emission rate or flow, is controlled by the control device 218. The control device can increase or decrease the ion flow rate by changing the conductance, which changes the impedance, Between the first and the second dissimilar materials 214, 216. By controlling ion exchange, system 210 can encode information in the ion exchange process. Thus, system 210 uses ionic emission to encode information in ionic exchange.
[00172] The control device 218 can vary the duration of a fixed ion exchange rate or current flow magnitude while keeping the rate an almost constant magnitude, similar to when the frequency is modulated and the amplitude is constant. Also, the control device 218 can vary the level of the ion exchange rate or the magnitude of the current flow while maintaining the duration almost constant. Thus, using various combinations of changes in duration and changing the rate or magnitude, the control device encodes information in the current flow or ion exchange. For example, the control device 218 can use, but is not limited to, any of the following techniques, namely, Binary Phase Shift Switching (PSK), Frequency Modulation, Amplitude Modulation, On-Off Switching, and PSK with on-off switching.
[00173] As indicated above, the various aspects described herein, such as systems 210, 220 of Figures 5 and 6, respectively, include electronic components as part of control device 218 of system 210 or control device 228 of system 220 Components that may be present include, but are not limited to: logic and / or memory elements, an integrated circuit, an inductor, a resistor, sensors to measure various parameters, 400 inductors, resonant circuits, and drive circuits for activate the inductor and / or the resonant circuits. Each component can be attached to the structure and / or to another component. The components on the support surface can be arranged in any convenient configuration. Where two or more components are present on the surface of the solid support, interconnections can be provided.
[00174] Referring now to Figure 8, system 260 includes a pH 256 sensor component connected to a third material 219, which is selected according to the specific type of detection function being performed, according to an aspect of this description. The pH sensor component 256 is also connected to the control device 218. The third material 219 is electrically isolated from the first material 214 by a non-conductive barrier 235. In one aspect, the third material 219 is platinum. In operation, the pH 256 sensor component uses the voltage potential difference between the first and second dissimilar materials 214, 216. The pH 256 sensor component measures the voltage potential difference between the first material 216 and the third material 219 and record this value for later comparison. The pH 256 sensor component also measures the voltage potential difference between the third material 219 and the second material 216 and records this value for later comparison. The pH sensor component 256 calculates the pH level of the surrounding environment using the voltage potential values. The pH sensor component 256 provides this information for control device 218. Control device 218 is coupled to switch 400 and controls current flow through inductor 401 to generate an electromagnetic field. In one aspect, the electromagnetic field can encode information relevant to the pH level in ion transfer, which can be detected by a receptor (not shown). Thus, system 260 can determine and provide information regarding the pH level to a source external to the environment.
[00175] Figure 9 illustrates a block diagram representation of the control device 218, in accordance with an aspect of the present description. Control device 218 includes a control component 242, a counter or clock 244, and a memory 246. Furthermore, control device 218 is shown including a sensor component 252 as well as the sensor component 254 which was initially referenced in Figure 7. Control component 242 has an input 248 electrically coupled to the first material 214 and an output 250 electrically coupled to the second material 216. Control component 242, clock 244, memory 246, and sensor components 252/254 also have power inputs (some not shown). The energy for each of these components is supplied by the voltage potential produced by the chemical reaction between the first and second materials 214, 216 and the electrically conductive fluid, when system 210 (Figures 1 and 7) is in contact with the electrically conductive fluid . Control component 242 controls conductance through logic that changes the total impedance of system 210. Control component 242 is electrically coupled to clock 244. Clock 244 provides a clock cycle for control component 242. Based on programmed characteristics of control component 242, when a specified number of clock cycles has passed, control component 242 changes the conductance of switch 400 (Figures 5, 7, 8) to control current flow through inductor 401 (Figures 5 , 7, 8) to encode information in an electromagnetic field. This cycle is repeated and thereby the control device 218 produces a unique current signature characteristic. Control component 242 is also electrically coupled to memory 246. Both clock 244 and memory 246 are powered by the voltage potential created between the first and second materials 214, 216.
[00176] Control component 242 is also electrically coupled to and in communication with the first and second sensor components 252, 254. In the aspect shown, the first sensor component 252 is part of the control device 218 and the second sensor component 254 is a separate component. In alternative aspects, any of the first and second sensor components 252, 254 can be used without the other and the scope of the present description is not limited by the structural or functional location of the sensor components 252 or 254. Furthermore, any component of the system 210 can be functionally or structurally moved, combined, or repositioned without limiting the scope of the present description as claimed. Thus, it is possible to have a single structure, for example, a processor, which is designed to perform the functions of all the following components: the control component 242, the clock 244, the memory 246, and the sensor component 252 or 254. On the other hand, it is also within the scope of this description to have each of these functional components located in independent structures that are electrically connected and capable of communicating.
[00177] Referring again to Figure 9, sensor components 252, 254 can include any of the following sensors: temperature, pressure, pH level and conductivity. An additional node can be configured as a reference electrode to allow anode and cathode measurement independently. In one aspect, the sensor components 252, 254 gather information from the environment and communicate the analog information to the control component 242. The control component then converts the analog information to digital information and the digital information is encoded in the electromagnetic field. In another aspect, the sensor components 252, 254 gather information from the environment and convert the analog information to digital information and then communicate the digital information to the control component 242. In the aspect shown in Figure 9, the sensor component 254 is shown as being electrically coupled to the first and second dissimilar materials 214, 216 as well as the control device 218. In another aspect, as shown in Figure 9, the sensor component 254 is electrically coupled to the control device 218 at a different connection point which acts as both a power supply source for the 254 sensor component and a communication channel between the 254 sensor component and the control device 218.
[00178] As indicated above, the control device 218 can be programmed in advance to emit a predefined electromagnetic coded signal. In another aspect, the system can include a receiver system that can receive programming information when the system is activated. In another aspect, not shown, switch 244 and memory 246 can be combined in one device.
[00179] In addition to the above components, system 210 (Figures 5 and 7) can also include one or another electrical or electronic component. Electrical or electronic components of interest include, but are not limited to: additional logic and / or memory elements, for example, in the form of an integrated circuit; an energy regulating device, for example, battery, fuel cell or capacitor; a sensor, a stimulator, etc .; a signal transmission element, for example, in the form of an antenna, electrode, inductor, etc .; a passive element, for example, an inductor, resistor, etc.
[00180] Figure 10 illustrates a first component 403, which comprises an inductor 402, according to an aspect of the present description. The first component 403 is configured in association with an integrated circuit 404 that has a cathode layer (not shown) on top of the integrated circuit 404. The integrated component 404 is associated with an ingestible identifier, such as an ingestible identifier 270 shown in Figures 12 and 13, for example. Returning to Figure 10, the integrated circuit component 404 is, for example, between 10 micrometers and 10 millimeters on one side, such as 100 micrometers to 5 millimeters, for example one millimeter on one side, having a cathode on a first side ( not shown) and an anode on a second side (not shown). The inductor 402 can be formed by depositing, engraving, or printing a patterned metal layer on the integrated circuit 404. The inductor 402 can comprise a dense metal pattern that defines a multiple spiral design, patterned in a spiral. The metal layer has slits cut into it, as does a single spiral slit cut. In other respects, inductor 402 can be a solenoid or a solenoid with a ferrite, without limitation. Inductor 402 is a component of a resonant circuit coupled to a drive circuit to generate an electrical signal that oscillates within inductor 402.
[00181] Figure 11 illustrates a second component 406 comprising an inductor 408, in accordance with an aspect of the present description. The second component 406 is configured in association with an integrated circuit 410 (integrated circuit or flexible electrode). The integrated circuit component 410 is, for example, between 10 micrometers and 10 millimeters on one side, such as 100 micrometers at 5 millimeters, for example one millimeter on one side, which has a cathode on a first side (not shown) and an anode on a second side (not shown). Integrated circuit 410 is embedded in a non-conductive membrane 412 by which a conductive transmission is generated by modulated current. The inductor 408 runs along, that is, it is associated with the perimeter of the integrated circuit 410. The inductor 408 includes, for example, a coil of multiple turns / multiple layers. In one aspect, inductor 408 is relatively small. In many respects, an insulating layer (not shown) is introduced over inductor 408 to extend the range. For example, the insulating layer includes several hundred microns of plastic over the 408 inductor.
[00182] With reference to Figures 10 and 11, in several aspects, the inductor 402, 408 can be configured according to any standard and / or location related to the pharmaceutical information technology of the life cycle. Patterns include, for example, spirals, squiggles, curves, multiple curves, straight lines, curves, single layer, multilayer, and other designs and design combinations.
[00183] Figure 12 illustrates an ingestible identifier 270 that includes an inductor 420, according to an aspect of the present description. In Figure 12, the ingestible identifier 270 includes an integrated circuit 272 and a non-conductive membrane 274 (e.g., skirt, electrically insulating element). The integrated circuit includes both a conductive communication component and an inductor 420.
[00184] Figure 13 is a side section view of the injectable identifier 270 shown in Figure 12. The ingestible identifier 270 is an integrated circuit 272 (also referred to here as the identifier) as well as upper and lower electrodes 276, 278, where the upper and lower electrodes 276, 278 are made of dissimilar materials and are configured so that when in contact with stomach fluid a current flows through the integrated circuit 272 to cause one or more functional blocks in the circuit to emit a detectable signal. Ingestible identifier 270 includes a non-conductive membrane 274 (sometimes referred to herein as a "skirt" or electrically insulating element), as previously discussed. The ingestible identifier 270 includes an inductor element 420 formed above one of the electrodes 276, as shown.
[00185] The ingestible identifier 270 can be used in conjunction with receivers configured to receive the electromagnetic field generated by the inductor component 420. An example of a dockable medical device is a transmitter / receiver, permanently associated with a body (such as implanted in body) or removably attachable to an external portion of a body. The ingestible identifier 270 can be communicatively associated with a transmitting device and / or receiver. The transmitting / receiving device includes devices within the body, external devices removably or permanently attachable to the body, and remote devices, that is, devices not physically associated with the body, but capable of communicating with the Ingestible Event Marker. Receivers of interest are discussed below in more detail below in connection with Figures 3, 47, 49, and 50-55, for example.
[00186] Various aspects of the devices and systems, including pills and packaging enabled a communication, allow the identification of the ingestible identifier 270 and any of its medication (if present). "Pill", as used below, is representative of any medication enabled in communication. The ingestible identifier package 270 includes, for example, a "blister" package capable of housing an individual ingestible identifier (such as a pill or a limited number of pills or capsules). The ingestible identifier package 270 further includes containers, boxes, wrappers, IV bags, and so on associated with the medication.
[00187] In several aspects, the communication components can be sovereign for the pill. In other respects, the communication components can be distributed, for example, physically associated with the packaging as well as the ingestible component, such as a pill or capsule.
[00188] Once the ingestible identifier 270 reaches the patient's environment, information associated with the ingestible identifier can be used for a variety of purposes. For example, the ingestible identifier 270 can interoperate with a container of the ingestible identifier 270 and with a receiver to ensure that the person trying to open the ingestible identifier container is actually the person for whom it is prescribed. Additional communication activities include an information control system, in which medication information associated with the ingestible identifier 270 is compared against patient data received from one or multiple sources to determine, for example, whether a medication is contraindicated, subject to appropriate dosage amounts and times or other events and / or conditions.
[00189] After ingesting the patient, the information stored in the ingestible identifier 270 can be retrieved from one or more of the communication components. For example, communication capabilities can be performed after ingestion through the electromagnetic field communication components, for example, using the receiver. Data can be stored in the ingestible identifier 270 and reprogrammed with a secure digital signature on each transaction.
[00190] When an expulsion of the patient from an ingestible identifier 270 has occurred, several aspects allow communication with a device such as a sensor to determine, for example, data related to the patient or medication, or time of transit through the body. Alternatively, in many ways, the data is erased (or several components / subcomponents associated with the data are destroyed or separated from the system) to protect privacy concerns after expulsion.
[00191] Having described the electromagnetic ingestible identifier perception and detection system at a general level in connection with Figures 1-13, the description now turns to specific implementations of an electromagnetic ingestible identifier perception and detection system that includes ( 1) an ingestible identifier pulse circuit and drive circuit comprising a low impedance inductor, (2) the ingestible identifier and inductor resonant circuit combined, (3) an impulse communication system and protocol, and (4) various receiver configurations to receive the electromagnetic signal transmitted by the ingestible identifier.
[00192] Figures 14-18 illustrate various configurations of an electromagnetic ingestible identifier perception and detection system, according to various aspects of the present description. Each of the ingestible identifiers illustrated in Figures 14-18 can be employed as the transmission component of the electromagnetic ingestible identifier perception and detection system according to various aspects of the present description.
[00193] Figure 14 illustrates an aspect of the ingestible identifier 200 shown in Figures 4A and 4B according to an aspect of the present description. The ingestible identifier 200 comprises an integrated circuit 202 and a non-conductive membrane 208 positioned between the dissimilar materials 204, 206 (Figure 4A) provided on the integrated circuit 202. As described here, the dissimilar materials 204, 206 generate a voltage potential for when the ingestible identifier 200 is immersed in an electrically conductive fluid. In one aspect, the ingestible identifier 200 shown in Figure 14 can be configured in the manner described in connection with Figures 5-9. In other words, the ingestible identifier 200 can be used in the perception and detection system based on the electromagnetic field as described here generating a coded signal within the individual's body shown in Figures 1 and 2.
[00194] Figure 15 illustrates an aspect of the ingestible identifier 270 shown in Figures 12-13, in accordance with an aspect of the present description. The ingestible identifier 270 comprises an integrated circuit 272, a non-conductive membrane 274, and an inductor 420 provided over the integrated circuit 272. As described here, dissimilar materials 274, 276 (Figure 13) generate a voltage potential to supply the circuit integrated 272 when ingestible identifier 270 is immersed in a conductive fluid. In one aspect, the ingestible identifier 272 can be configured in the manner described in connection with Figures 12-13.
[00195] With reference back to Figure 15, inductor 420 can be standardized as shown in Figures 10 and 11, for example, without limitation. The inductor 420 is a component of a resonant circuit and is driven by a drive circuit component of integrated circuit 272. The driven resonant circuit generates an electromagnetic signal that can be detected by a receiver external to the individual.
[00196] In one aspect, the ingestible identifier 270 is generally composed of a single piece of Si material formed in a single semiconductor manufacturing process. Consequently, the metals used in the semiconductor manufacturing process used to make integrated circuit 272 can be used to make ingestible identifier 270 and inductor 420. Thus, the resonant circuit comprising inductor 420 and a capacitor can be formed on the integrated circuit 272 during the semiconductor manufacturing process.
[00197] The inductor 420 can be formed on the integrated circuit 272 of the ingestible identifier 270 using a variety of techniques. In one aspect, inductor 420 can be formed as (1) a spiral from the bottom of integrated circuit 272 to the top of integrated circuit 272 where the different layers are interconnected via paths. In another aspect, inductor 420 can be formed as (2) a first layer of metal on one side of integrated circuit 272 from an external portion of integrated circuit 272 to an internal portion and a second layer of metal is formed on top of the first layer of metal. Inductor 420 can comprise four stacked layers of inductors and eight different nodes to drive inductor 420. In another aspect, inductor 420 can be formed as (3) two separate inductors with a central tap to match any parasitic degradations in the signal.
[00198] Figure 16 illustrates an ingestible identifier 280 comprising an integrated circuit 282 and a separate inductor component 430 formed on a separate substrate 440, in accordance with an aspect of the present description. Consequently, the ingestible identifier 280 can be manufactured in two separate processes as two separate substrates which are subsequently interconnected. In one aspect, the ingestible identifier 280 comprises an integrated circuit 282, a passive integrated device (IPD) component 450, and optionally a non-conductive membrane 288. The IPD component 450 is a passive device that is integrated with integrated circuit 282 Integrated circuit 282 comprises dissimilar materials provided thereon to generate a voltage potential when in contact with an electrically conductive fluid, where the voltage potential feeds integrated circuit 282, as described in connection with Figures 4A-4B. and 5- 9. The non-conductive membrane 288 can be interposed between the dissimilar materials to extend the flow path of the electric current between the dissimilar materials. The inductor 430 on the IPD component 450 is formed on a separate substrate 440 and is electrically coupled to the outlet of circuit 282.
[00199] Integrated circuit 282 can be manufactured using a first complementary metal oxide semiconductor (CMOS) process on a single Si 284 substrate. Inductor 430 and a capacitor can be manufactured using a second process on a second substrate 440 chip to produce the IPD 450 component. The IPD 450 component can employ high quality metals to build inductor 430 on a secondary 440 integrated circuit (IC) substrate substrate. The 282 integrated circuit portion of the ingestible identifier 280 and the IPD 450 component can then be stacked together with further processing such as deposition, drilling, etc., if necessary. The process would generate a single semiconductor (e.g., Si) from two separate chip substrates 284, 440. The two separate semiconductor substrates 284, 440 can be combined or linked using various techniques such as molecular connection, for example. If the optional non-conductive membrane 288 is used, the integrated circuit 282 can be located over the non-conductive membrane 288 (for example, exit). In another aspect, a ReDistribution Layer (RDL) can be used to implement inductor 430. In another aspect, the inductor can be formed on a glass substrate instead of a semiconductor substrate.
[00200] Figure 17 illustrates an ingestible identifier 290 comprising an inductor 460 formed on a non-conductive membrane 294, in accordance with an aspect of the present description. The ingestible identifier 290 comprises an integrated circuit 292, a non-conductive membrane 294, and an inductor 460 formed on the non-conductive membrane 294. Integrated circuit 292 comprises dissimilar materials formed on it to generate a voltage potential when in contact with a electrically conductive fluid and generate a conductive current in the fluid, as described in connection with Figures 4A-4B and 5-9. The non-conductive membrane 294 is interposed between the dissimilar materials to extend the flow path of the electric current. The inductor 460 can be manufactured on the non-conductive membrane 294 using various processes such as deposition, printing and the like. Inductor 460 is electrically coupled to integrated circuit 292.
[00201] Figure 18 illustrates an ingestible identifier 295 comprising an inductor 470 on one or both of the dissimilar materials 274, 276 (Figure 13) after the dissimilar materials 274, 276 are deposited on the integrated circuit 272, according to one aspect of this description. The capacitor portion of the resonant circuit can be formed either during the semiconductor manufacturing process or later. In one aspect, the separate semiconductor pads can be bonded together and connected to the dissimilar materials of the ingestible identifier (eg Mg and CuCI) via a Si process and filled with metallic copper (Cu). The process can be carried out on one side or both sides of the matrix and then singled out to produce components.
[00202] Figure 19 is a schematic representation of an ingestible identifier 270 comprising an inductor 420 and a single-ended inductor drive circuit 500, in accordance with an aspect of the present description. The single-ended drive circuit 500 is configured to drive inductor 420. The drive circuit 500 is powered by the partial battery 501 formed by the dissimilar materials 274, 276, as previously discussed in connection with Figures 12-13, immersed in an electrically conductive fluid. A control device 422 controls the switch SW which is connected in series with the inductor 420. The switch SW comprises an input terminal 424, an output terminal 426, and a control terminal 428. The control device 422 is coupled to the control terminal 428 of the SW switch to control the operation of the SW switch. For example, the control device 422 can be configured to open and close the SW switch to generate an oscillating RF current through inductor 420, which generates an electromagnetic RF signal. The SW switch can be opened and closed in a predefined mode to generate an encoded RF electromagnetic signal. The electromagnetic RF signal can be transmitted through body tissues. The electromagnetic F signal of R can be detected by an external or internal receiving device that has a magnetic signal detection mechanism.
[00203] Figure 20 is a schematic representation of an ingestible identifier 271 comprising an inductor 420 and a push-pull H type 502 inductor drive circuit 504, in accordance with an aspect of the present description. The drive circuit 502 of the push-pull bridge type 504 is configured to drive the inductor 420. The drive circuit 502 is powered by the partial battery 501 formed by the dissimilar materials 274, 276, previously discussed in connection with the Figures 12-13, immersed in an electrically conductive fluid. The inductor 420 is connected between two nodes of the H 504 bridge which comprises at least four switches SW1, SW2, SW3, SW4 in a floating configuration. Each of the switches SW1, SW2, SW3, SW4 comprises an input terminal, an output terminal, and a control terminal. A control device 430 is coupled to the control terminal of each of the switches SW1, SW2, SW3, SW4 to control the conductance of the switches SW1, SW2, SW3, SW4. For example, the control device is configured to open and close switches SW1, SW2, SW3, SW4 in a predefined mode to generate an oscillating current through inductor 420, which generates an encoded RF magnetic signal. In one aspect, two of the switches SW1, SW2 on bridge H 504 are closed at once to conduct a current (i) i through inductor 420 while the other two switches SW3, SW4 remain open. Then, two of the switches SW3, SW4 on the bridge H 504 are closed at once to conduct a current (i) 2 through inductor 420 while the other two switches SW1, SW2 remain open. The pair of switches (SW1, SW2) and (SW3, SW4) are alternately connecting inductor 420 between the positive and partial battery return terminals 501 to alternately conduct current (i) i 1 and (i) 2 through inductor 420.
[00204] Control device 430 operates switches SW1, SW2, SW3, SW4 to connect two of the switches in series with inductor 420 for a half cycle. Thus control device 430 drives inductor 420 twice per cycle to double the signal while placing a constant load on battery 501. For example, in one aspect, the control device operates two of the switches SW1, SW2 in a first phase ψi and the other two switches SW3, SW4 in a second phase ψ2, where the first phase ψi is 180 ° out of phase with the second phase ψ2. Consequently, during the first half of the cycle, switches SW1 and SW2 are closed and switches SW3 and SW4 are opened to generate a first current (i) i through inductor 420. During the second half of the cycle, switches SW3 and SW4 they are closed and switches SW1 and SW2 are opened to generate a second current (i) 2 through inductor 420 in the opposite direction of the first current (i) i. In a cycle, inductor 420 is activated by h and Í2 to double the output signal. Consequently, as the pair of switches SW1, SW4 and SW2, SW3 are cycled on and off by the control device, an oscillating current encoded through inductor 420 is generated, which in turn generates an electromagnetic RF signal that can be transmitted through body tissues. The electromagnetic RF signal can be detected by an external or internal receiver device that has a magnetic signal detection mechanism.
[00205] Figure 21 is a schematic representation of an ingestible identifier 270 comprising an inductor 420 and a drive circuit of a single-ended inductor 422, in accordance with an aspect of the present description. The single-ended drive circuit for 422 is configured to drive inductor 420. Drive circuit 422 is powered by a partial battery formed by electrically coupling dissimilar materials 274, 276 immersed in an electrically conductive fluid, as previously discussed in connection with Figures 12-13. As shown in Figure 21, the battery portion of the ingestible identifier 270 is divided so that the energy applied to the control device 506 is isolated from the energy applied to the inductor 420. The SW switch comprises an input terminal 507, an output 509, and a control terminal 511. A control device 506 is coupled to the single-ended drive circuit 422, which is coupled to the control terminal 511 of the SW switch to control the conductance of the SW switch. Under the control of the control device 506, the single-ended drive circuit 422 operates the SW switch connected in series with the inductor 420. The SW switch is opened and closed by the control device 506 to generate an oscillating current encoded through the inductor 420, which generates an electromagnetic RF signal. The electromagnetic RF signal can be transmitted through body tissues with little or no attenuation. The magnetic RF signal can be detected by an external or internal receiver device that has a magnetic signal detection mechanism.
[00206] Figure 21A is a schematic representation of an ingestible identifier 270A comprising an inductor 420 and a single-ended inductor drive circuit 422 where a first metallic layer 274 is divided into two regions and a second metallic layer 276 is divided in two regions, according to one aspect of the present description.
[00207] Figure 22 is a schematic representation of an ingestible identifier 271 comprising an inductor 420 and a push-pull H type 504 inductor drive circuit 504, in accordance with an aspect of the present description. The H30 push-pull inductor drive circuit 430 504 is configured to drive inductor 420. The drive circuit 430 is powered by the partial battery formed by dissimilar materials 274, 276 immersed in an electrically conductive fluid, such as previously discussed in connection with Figures 12-13. As shown in Figure 22, the battery portion of the ingestible identifier 270 is divided so that the energy applied to the control device 506 is isolated from the energy applied to inductor 420. Inductor 420 is connected between two nodes of the H 504 bridge comprising at least four switches SW1, SW2, SW3, SW4 in a floating configuration. In one aspect, two of the switches on the H 504 bridge are closed at once to allow current to flow through inductor 420 while the other two switches remain open, alternately connecting inductor 420 between the positive and battery return terminals. Each of the switches SW1, SW2, SW3, SW4 comprises an input terminal, an output terminal, and a control terminal. A control device 506 is coupled to the H 50 push-pull type 504 inductor drive circuit 504 which is coupled to the control terminals of switches SW1, SW2, SW3, SW4 to control the conductance of switches SW1, SW2 , SW3, SW4.
[00208] Under control of the control device 506, the push-pull bridge type 430 inductor drive circuit 504 operates switches SW1, SW2, SW3, SW4 to connect two of the switches in series with inductor 420 for a half cycle. Thus inductor 420 is activated twice per cycle to double the signal while placing a constant load on battery 501. For example, in one aspect, the drive circuit 430 operates two of the switches SW1, SW2 in a first phase ei and the two other switches SW3, SW4 in a second phase ψ2, where the first phase ψi is 180 ° out of phase with the second phase ψ2. Consequently, during the first half of the cycle, switches SW1 and SW2 are closed and switches SW3 and SW4 are opened to generate a first current (i) i through inductor 420. During the second half of the cycle, switches SW3 and SW4 they are closed and switches SW1 and SW2 are opened to generate a second current (i) 2 through inductor 420 in the opposite direction of the first current (i) i. Thus, in a cycle, inductor 420 is activated by ii and Í2 to double the output signal. Consequently, as the pair of switches (SW1, SW2) and (SW3, SW4) are cycled on and off by the control device 430, an oscillating current encoded through inductor 420 is generated, which in turn generates an electromagnetic signal of RF that can be transmitted through body tissues with little or no attenuation. The magnetic RF signal can be detected by an external or internal receiver device that has a magnetic signal detection mechanism.
[00209] The SW, SW1, SW2, SW3, SW4 switches described in connection with Figures 19-22 can be implemented as solid-state electronic switching elements such as semiconductor switching elements, which include, for example, transistors, field effect transistors (FET), metal oxide semiconductor (MOSFET) FETs, bipolar junction transistors, and any suitable equivalents.
[00210] Figure 22A is a schematic representation of an ingestible identifier 271A comprising an inductor 420 and a push-pull H type inductor drive circuit 430 where a first metallic layer 274 is divided into two regions and one second metallic layer 276 is divided into two regions, according to one aspect of the present description.
[00211] Figure 23 illustrates an inductive element 508 or inductor structure formed on an insulating substructure 514, which can be used as the inductive element in an ingestible identifier integrated circuit, according to an aspect of the present description. For example, a flat-type inductor 508 formed over a semiconductor substrate 512. As shown in Figure 23, such a flat-type inductor structure 508 typically has a spiral configuration which includes a conductive metal strip or spiral 510 formed over a semiconductor substrate 512 through an insulating layer 514 on the substrate. The conventional square-shaped inductance value shown in Figure 23 can be expressed as the following equation: (1):

[00212] Where L is the inductance (nH), d is a length (mm) of the outermost dimension of the spiral-inducing metallization layer 510, foot a width (mm) of the spiral-inducing metallization layer 510 , q is the spacing (mm) between two neighboring regions of the spiral-shaped metallization layer 510, and r is a ratio of p / q, that is, (p / q). When p = q, the above equation is simplified to the following equation (2):

[00213] For example, if p = q = 0.05 mm and d = 0.5 mm, the inductance L is calculated from equation (1) or (2) above as approximately 2 nH.
[00214] The 508 flat inductor construction described above increases the level of integration for the circuit, reducing the number of circuit elements located outside the chip together with the attendant need for complex interconnections. Recently, however, to decrease the size and cost of manufacturing semiconductor integrated circuit devices, not only the active components (eg, transistors), but also passive components (eg, inductors and capacitors) have been required to be miniaturized each more. Consequently, for the plane-type inductors above, attempts have been made to address the miniaturization requirement by decreasing the size of the spiral-shaped conductor layer 510. That is, reducing the size of the width p and the interval q-
[00215] For example, if p = 0.006 mm, q = 0.006 mm and d = 0.15 mm, the inductance L is calculated from the above equation (1) to be approximately 2.5 nH. If the spiral-shaped metallization layer or conductor layer 510 having this dimension is formed on a GaAs substrate, the interline capacitance C of the conductor layer 510 is approximately 0.06 pF. This value is obtained by approximating the two neighboring regions of the spiral-shaped conductor layer 510 as coplanar strip lines. The resonance frequency fo in this case is approximately equal to 12.5 GHz, where fo is defined as the following equation (3):

[00216] To reduce the plane size of the spiral-shaped inductor metallization or conductor layer 510 to, say, 70% of its original size, if the above parameters are designated as p = 0.0024 mm and q = 0.001 mm , inductance L can be maintained at approximately 2.5 nH. However, the C interline capacitance of conductor 510 increases to approximately 0.28 pF and, as a result, the resonance frequency fo will decrease to approximately 6.0 GHz, which is lower than the case of the original size by approximately 6.5 GHz. Consequently, with inductor 508 shown in Figure 23, when the q interval of the neighboring regions of the spiral-shaped conductor layer 510 is decreased for miniaturization, the interline capacitance C will increase and the resonance frequency fo will decrease and consequently, the maximum operating frequency is decreased.
[00217] Figure 24 illustrates a multi-layer inductive element 520 or inductor structure formed on an insulating substructure 526, 528, which can be used as the inductive element in an ingestible identifier integrated circuit, according to an aspect of the this description. An example of a multilayer inductor configuration is illustrated in Figure 24. As seen in Figure 24, the multilayer inductor structure 520 is manufactured with a first and second metallization levels that constitute respective spiral inductor sections 522, 524. Each inductor section 522, 524 is formed on a corresponding insulating layer 526, 528, and is connected end to end by a centrally located conductive path 530. In comparison with the flat structure 508 shown in Figure 23, the arrangement of multiple The layers of Figure 24 provide a substantial increase in inductance per unit area, as well as a reduction in dimension d.
[00218] Figures 25-27 illustrate a two-port, two-port, 600-layer inductor configuration, in accordance with an aspect of the present description. The two-port two-layer inductor configuration 600 of example 250 shown in Figure 25 comprises two inductor sections 602, 604 formed on two corresponding insulating layers 608, 610 of a semiconductor integrated circuit 601 and are connected end to end by a first centrally located conductive path 606. Two ports A1 (Port 1), A2 (Port 2) for connecting inductor 600 to other circuit elements are located on an upper layer 603 of semiconductor integrated circuit 601. The second port A2 of the second section of inductor 604 is connected to the upper layer 603 of semiconductor integrated circuit 601 by a second conductive path located off center 607. Although Figures 25-27 show a two-layer inductor two ports 600, the present description contemplates an inductor of n n-gate layers comprising a plurality of n inductor sections formed on n corresponding insulating layers of an in circuit integrated semiconductor array in series, parallel, or any combination thereof suitable for one or more conductive pathways, where n is an integer greater than 2. An example of a multilayer inductor with more than two layers is shown in Figures 28-30, which show a two-layer, four-port inductor comprising sections of inductor 614, 616, 618, 620 formed on corresponding insulating layers 622, 624, 626, 628 of a semiconductor integrated circuit and interconnected end to end via a centrally located conductive path.
[00219] Figure 26 is a two-port two-layer inductor diagram 600 shown in Figure 25, in accordance with an aspect of the present description. The two-layer two-port inductor 600 is shown as two separate inductor sections 602, 604 for clarity of illustration. The first section of inductor 602 is formed on a first insulating layer 608 and a second section of inductor 604 is formed on a second insulating layer 610 of a semiconductor integrated circuit 601. The first and second sections of inductor 602, 604 are connected in series through a conductive path 606 shown in dashed line. Connections for the two ports A1 (Port 1), A2 (Port 2) are provided on an upper layer 603 of the semiconductor integrated circuit 601. The connection for the second port A2 is provided via a conductive path 607.
[00220] Figure 27 is a schematic representation of the two-port two-layer inductor 600 shown in Figures 25 and 26, in accordance with an aspect of the present description. The first section of inductor 602 is designated as L1 and the second section of inductor 604 is designated as L2. Ends B1, B2 of inductor sections L1, L2 are connected in series via a conductive path 606. Inductor 600 can be coupled to a circuit element via the two ports A1 (Port 1), A2 (Port 2). Since inductor sections 602, 604 (L1, L2) are formed as coils on adjacent insulating layers 608, 610 of a semiconductor integrated circuit 601, the current (i) flowing in an inductor section 602 induces a voltage in the section adjacent inductor 604 by means of mutual inductance. As shown in Figure 27, current (i) flows in the same direction through the first and second inductor sections 602, 604.
[00221] Figures 28-30 illustrate the two-port 612 four-layer inductor configuration in accordance with an aspect of the present description. The four-layer, two-port inductor configuration 612 shown in Figure 28 comprises four sections of inductor 614, 616, 618, 620 formed on four corresponding insulating layers 622, 624, 626, 628 of a semiconductor integrated circuit 611 and are connected to the end with end through conductive tracks 630, 632, 634, 635, according to an aspect of the present description. Two ports A1 (Port 1), A4 (Port 2) are provided on an upper layer 613 of semiconductor integrated circuit 611 to connect inductor 612 to other circuit elements. The second port A4 is coupled to the fourth inductor section 620 and is connected to the upper layer 613 of the semiconductor integrated circuit 611 by a conductive path 634.
[00222] Figure 29 is a four-layer, two-port inductor 612 inductor diagram shown in Figure 28 according to an aspect of the present description. The two-layer four-port inductor 612 is shown as four separate inductor sections 614, 616, 618, 620 for clarity of illustration. Each of the inductor sections 614, 616, 618, 620 is formed on a separate insulating layer 622, 624, 626, 628 and is connected in series via conductive pathways 630, 632, 634, 635. A connection between A4 (Door 2) for the upper layer 613 of the semiconductor integrated circuit 611 is provided via a conductive path 635. Connections for ports A1 (Port 1) and A4 (Port 2) are provided over an upper layer 613 of the semiconductor integrated circuit 611 .
[00223] Figure 30 is a schematic representation of two-layer inductor two ports 612 shown in figures 28 and 29, in accordance with an aspect of the present description. The first section of inductor 614 is designated as L1, the second section of inductor 616 is designated as L2, the third section of inductor 618 is designated as L3 and the fourth section of inductor 620 is designated as L4. The inductive sections L1-L4 are connected end to end in series via conductive paths 630, 632, 634. Inductor 612 can be coupled to a circuit element through the two ports A1 (Port 1), A4 (Port 2). As the inductor sections 614, 616, 618, 620 (L1-L4) are formed as coils on adjacent layers 622, 624, 626, 628 of a semiconductor integrated circuit 611, the current (i) flowing in a section of inductor 614 induces a voltage in an adjacent inductor section 616, and so on, by means of mutual inductance. As shown in Figure 30, current (i) flows in the same direction through the first, second, third and fourth sections of inductor 614, 616, 618, 620 (L1-L4).
[00224] Figures 31-33 illustrate a n-layer inductor configuration on ports 630, in accordance with an aspect of the present description. The n-layer n-port inductor configuration 630 shown in Figure 31 comprises n-inductor sections 633, 636, 637, 638 formed on n corresponding insulating layers 640, 642, 644, 646 of a semiconductor integrated circuit 631 according to a aspect of this description. Each of the inductor n sections 633, 636, 637, 638, formed on n separate corresponding insulating layers 640, 642, 644, 646 is a mirror image of that above it. As shown in Figure 31, the n inductor sections 633, 636, 637, 638 are not interconnected, but instead are arranged as n individual inductor sections 633, 636, 637, 638. The n inductor sections 633, 636, 637, 638 can be interconnected to each other and other circuits in any suitable mode by 2n ports A1 (Port 1), B1 (Port 2), A2 (Port 3), B2 (Port 4), A3 (Port 5), B3 (Port 6), An (Port (2n-1)), Bn (Port 2n).
[00225] Figure 32 is a diagram of n-layer inductor n ports 630 shown in Figure 31, in accordance with an aspect of the present description. The n-layer inductor n ports 630 is shown as separate n inductor sections 633, 636, 637, 638 for clarity of illustration. The first section of inductor 633 is formed on a first insulating layer 640, the second section 636 is formed on a second insulating layer 642, the third section of inductor 637 is formed on a third insulating layer 644, and the umpteenth section of inductor 638 it is formed on the umpteenth insulating layer 646. Each of the inductor sections defines a coil that is a mirror image of a coil above it. Inductor sections 633, 636, 637, 638 are not connected, but are individually formed instead. The n pairs of ports (A1 (Port 1), B1 (Port 2)), (A2 (Port 3), B2 (Port 4)), (A3 (Port 5), B3 (Port 6)), (An Ports (2n-1)), Bn (Ports 2n)) can be provided on n separate insulating layers to connect individual inductor sections 630 to a circuit in any predetermined configuration.
[00226] Figure 33 is a schematic representation of n-layer inductor n ports 630 shown in Figures 31 and 30 according to an aspect of the present description. The first section of inductor 633 is designated as L1, the second section of inductor 636 is designated as L2, the third section of inductor 637 is designated as L3, and the umpteenth section of inductor 638 is designated as Ln. As shown in Figure 33, the L1-Ln inductor sections are not interconnected and can be individually coupled to a circuit element through the n pairs of ports (A1 (Port 1), B1 (Port 2)), (A2 (Port 3)), B2 (Port 4), (A3 (Port 5), B3 (Port 6)), (An (Port (2n-1)), Bn (Port 2n)) in any predetermined configuration. As inductor sections 633, 636, 637, 638 (L1- Ln) are formed as adjacent insulating layers of individual coils 640, 642, 644, 646 of a semiconductor integrated circuit 631, the current flowing in an inductor section 633 induces a voltage in an adjacent inductor section 636, and so on, by means of mutual inductance.
[00227] Figures 34-36 illustrate a two-port three-layer inductor 650 with a central branch connection configuration 653, in accordance with an aspect of the present description. The three-port, two-layer inductor 650 with a central branch connection configuration 653 shown in Figure 34 comprises four sections of inductor 652, 662, 664, 654 formed on two corresponding insulating layers 658, 660 of a semiconductor integrated circuit 651 and are connected end to end through conductive pathways 653, 656, 657, 668. Three ports A1 (Port 1), A4 (Port 2), (Port 3) for connecting inductor 650 to the others the circuit elements are located on a upper layer 655 of semiconductor integrated circuit 651. This geometry allows the construction of two layers of symmetrical coils with two layers of metal while symmetrical coils, traditional central derivatives require two layers per coil. Consequently, the present geometry provides more turns in the same matrix area.
[00228] Figure 35 is a two-layer, three-port inductor diagram 650 with a center branch connection 653 shown in Figure 34, in accordance with an aspect of the present description. The three-layer, two-port inductor 650 with a center tap connection 653 is shown as four separate inductor sections 652, 662, 664, 654 for clarity of illustration. The first and second sections of inductor 652, 662 are formed on a first insulating layer 658 and the third and fourth sections of inductor 664, 654 are formed on a second insulating layer 660. The second section of inductor 654 is a mirror image of the first section of inductor 652. The first, second, third and fourth sections of inductor 652, 662, 664, 654 are connected in series via conductive pathways 653, 656, 657, 668 shown in dashed line. The connections for the three ports A1 (Port 1), A4 (Port 2), A2 / A3 (Port 3) can be provided over an upper layer 655 of the semiconductor integrated circuit 651.
[00229] Figure 36 is a schematic representation of inductor 650 shown in Figures 34 and 35, in accordance with an aspect of the present description. In the schematic diagram, the first section of inductor 652 in the two-layer inductor three ports 650 is referred to as L1, the second section of inductor 654 is referred to as L2, the third section of inductor 664 is referred to as L3, and the fourth section of inductor 654 is referred to as L4. Inductors L1, L2, L3, L4 are connected in series via connections 656, 657, 668. As inductors L1, L2, L3, L4 are formed as coils 652, 654 on adjacent layers 658, 660 of an integrated circuit of semiconductor 651 the current flowing in a coil 652 induces a voltage in the adjacent coil 654 by means of mutual inductance. As shown, current (i) flows through each of the inductors L1, L2, L3, L4 in the same direction.
[00230] Figure 37 is a schematic diagram of a resonant (oscillatory) inductor drive circuit 700, according to an aspect of the present description. The inductor drive circuit 700 adds a negative resistance (-R) using cross-coupled MOSFET transistors 702, 704 that manifests itself as a negative resistance (-R) which provides a self-oscillating behavior. The port of the first MOSFET transistor 706 is coupled to drain 708 of the second MOSFET transistor 704. Likewise, port 710 of the second MOSFET transistor 704 is coupled to drain 712 of the first MOSFET transistor 702. An inductor L comprises an inductor section 714 similar to the inductor sections described here. A supply voltage VDD is coupled to the Leo inductor substrate 716 is coupled to Vss. Inductor L comprises two ports P1 and P2 to connect inductor L to other circuit elements such as cross-coupled MOSFET transistors 702, 704. In the example in Figure 37, inductor L is coupled through drains 712, 712 of the first and second MOSFET transistors 702, 704, where port 1 (P1) of inductor L is coupled to drain 712 of the first MOSFET transistor 702 and port 2 (P2) of inductor L is coupled to drain 708 of the second MOSFET transistor 704. One capacitor C is coupled through drains 712, 712 of the first and second MOSFET transistors 702, 704 to adjust the oscillation frequency of the inductor drive circuit 700. Alternatively, the parasitic capacitance of inductor L can be used to adjust the oscillation frequency . Cross-coupled MOSFET transistors 702, 704 provide a current that oscillates within inductor L. This provides a reasonable Q, defined as the loss of power in a power cycle compared to the energy instituted in inductor L in a cycle. A sufficiently high Q provides adequate energy stored in the L inductor and provides a higher current to make a system more efficient. It will be appreciated that other types of negative resistance circuits can be used other than that illustrated in Figure 37.
[00231] Figure 38 is a block diagram of a pulse inductor drive circuit 720, according to an aspect of the present description. The inductor drive circuit 720 is used to push a signal through the inductor sections L1, L2, L3, L4 provided over individual layers of a semiconductor integrated circuit. Instead of coupling the inductor sections L1, L2, L3, L4 to an oscillator, a current pulse is created that decays exponentially over time. The charge can be stored in a capacitor and can be discharged. As shown in Figure 38, the pulse inductor drive circuit 720 comprises a battery voltage doubler section 722 coupled to a pulse generator circuit 724, which is coupled to a coil discharge circuit 726. In the illustrated example in Figure 38, pulse generator circuit 724 is coupled to four inductor discharge circuits 726, 728, 730, 732. It will be appreciated, however, that up to n inductor discharge circuit can be coupled to pulse generator circuit 724 without departing from the scope of this description. As discussed here, inductor drive circuit 720 pumps charge into a capacitor and then discharges the capacitor within inductor sections L1, L2, L3, L4 over a very short discharge cycle in relation to the active cycle.
[00232] The inductor discharge circuits 726, 728, 730, 732 are coupled to the pulse generator circuit 724 in parallel. In this "charge pump" configuration, the inductor discharge circuit structures 726, 728, 730, 732 are provided in parallel branches 734, 736, 738, 740 to provide four times the current instead of stacking them to provide four times the voltage. N layers of inductors can be configured to provide N capacitors. The inductor sections L1, L2, L3, L4 can be connected to be single-phase instead of alternating current (AC). As described herein, each inductor section L1, L2, L3, L4 includes two ports P1 and P2 for coupling inductor sections L1, L2, L3, L4 to corresponding inductor discharge circuits 726, 728, 730, 732.
[00233] Figure 39 is a schematic diagram of the impulse inductor drive circuit 720 shown in Figure 38, according to an aspect of the present description. The inductor drive circuit 720 is used to push a signal through the inductor sections L1, L2, L3, L4, provided on individual layers of a semiconductor integrated circuit. The battery voltage doubler circuit 722 quadruples the VBAT battery voltage, which is applied to each of the inductor discharge circuits 726, 728, 730, 732. The pulse generator circuit 724 applies impulses to each of the voltage circuits inductor discharge 726, 728, 730, 732, which drive the corresponding inductor sections L1, L2, L3, L4. Detailed descriptions of the battery voltage doubling circuit 722 of the pulse generator circuit 724 and the inductor discharge circuit 726, 728, 730, 732 are provided in connection with Figures 40-43.
[00234] Figure 40 is a block diagram of the battery voltage duplicating circuit 722 shown in Figures 38 and 39, according to an aspect of the present description. The battery voltage doubler circuit 722 includes a battery voltage VBAT 742 coupled to the input of a first voltage doubler circuit 744 and the output of the first voltage doubler circuit 2 * VBAT 744 is coupled to the input of a second voltage doubler circuit 746. The output of the second voltage doubler circuit 4 * VBAT 746 is applied to the pulse generator circuit 724 and to the inductor discharge circuits 726, 728, 730, 732.
[00235] Multiplier 744, 746 can be used where the supply voltage (of a battery, for example) is lower than the voltage required by the circuit. MOSFET circuits are commonly the standard logic block in many integrated circuits. For this reason, diodes are often replaced by this type of transistor, but wired to function as a diode - a diode-bound MOSFET arrangement. Capacitors C1, C2, C3 stabilize the VBAT battery output voltages, the first 2 * VBAT 744 voltage doubler circuit, and the second 4 * VBAT 746 voltage doubler circuit.
[00236] In one aspect, each voltage doubler circuit 744, 746 may comprise a charge pump, or multiplier, comprising a cascade of diode / capacitor cells with the bottom plate of each capacitor driven by a train of clock pulses supplied by clock oscillator circuits 748, 750. The circuit takes a VBAT DC input from system battery 742 with the clock trains providing the switching signal. The multiplier usually requires alternating cells to be triggered from opposite phase clock pulses.
[00237] Figure 41 is a schematic diagram of a voltage doubler circuit stage 744 (746) shown in Figure 40, in accordance with an aspect of the present description. Cross-coupled switched capacitor circuits continue to supply power when it has discharged below one volt. Duplicate voltage circuit 744 (746) comprises a switched capacitor stage 752 and clock stage 754. Clock stage 754 receives a pulse train at the CLK clock input of clock oscillator circuit 748 (750) and produces opposite phase clock pulses ψ1 and ψ2. When clock ψ1 is low, transistors Q1 and Q4 are turned on and transistors Q2 and Q3 are turned off and capacitor C4 voltage is applied to the Vout output. At the same time the clock ψ2 is high by turning off transistors Q6 and Q7 and turning on transistors Q5 and Q8, resulting in capacitor C5 being charged to Vin. When the clock ψ2 becomes low, the voltage across capacitor C5 is pushed to double Vin (2Vin), transistors Q6 and Q7 are turned on and transistors Q5 and Q8 are turned off, and 2Vin is applied to the output so that Vout = 2Vin. In the next half cycle the roles are reversed so that clock ψ1 is high and clock ψ1 is low, transistors Q1 and Q4 are turned off and transistors Q2 and Q3 are turned on to charge capacitor C4 to Vin. At the same time, transistors Q6 and Q7 are turned off and transistors Q5 and Q8 are connected so that the voltage at C5, 2Vin, is applied to the output. When the clock ψ1 becomes low, the voltage across capacitor C4 is pushed to double Vin (2Vin), transistors Q1 and Q4 are turned on and transistors Q2 and Q3 are turned off, and 2Vin is applied to the output so that Vout = 2Vin. Thus, the Vout output is supplied with 2Vin alternately on each side of the circuit.
[00238] The implementation of the voltage duplicator circuit stage 744 (746) described in Figure 41 provides a low loss because there are no diode connected MOSFETs and their associated limit voltage problems. Circuit 744 (746) also has the advantage that the ripple frequency is doubled because there are effectively two voltage doubling circuits both supplying the out-of-phase clock output ψ1, ψ2.
[00239] Figure 42 is a schematic diagram of the pulse generator circuit 724 shown in Figures 38 and 39, according to an aspect of the present description. The pulse generator circuit 724 comprises a first and second Schmitt triggers 758, 760, an RC circuit comprising R1 and C6 for adjusting a time constant delay T at the input of the second "delayed" Schmitt trigger 760, an inverter 762 , and a NOR 764 logic gate. In electronics, a Schmitt trigger 758, 760 is a comparator circuit with hysteresis implemented by applying positive feedback to the non-inverted input of a comparator or differential amplifier. This is an active circuit that converts an analog input signal to a digital output signal. The circuit is called a "trigger" because the output retains its value until the input changes sufficiently to trigger a change. In the non-inversion configuration, when the input is higher than a chosen limit, the output is high. When the input is below a different chosen limit (lower) the output is low, and when the input is between the two levels the output retains its value. This double-limit action is called hysteresis and implies that the Schmitt 758, 760 trigger has a memory and can act as a bistable multivibrator (hitch or flip-flop). There is a close relationship between the two types of circuits: a Schmitt trigger can be converted into a hitch and a hitch can be converted into a Schmitt trigger.
[00240] A first oscillator 756 provides a clock train for the input 766 of the first trigger of Schmitt 758 and simultaneously for the input of the resistor R1 of the circuit of R1, C6. Thus, the clock signal that appears at the input 770 of the second Schmitt trigger 760 is delayed by T defined by the circuit of R1, C6. Consequently, assuming that the first and second Schmitt triggers 758, 760 have similar internal propagation delay properties, the output 774 of the second "delayed" Schmitt trigger 760 is delayed from the output 772 of the first Schmitt trigger 758 by a constant of time T = R1 * C6 seconds. Output 772 of the first "non-delayed" Schmitt trigger 758 is converted by inverter 762 and output 776 of inverter 762 is applied to input A of NOR gate 764. Output 774 of the second "delayed" Schmitt trigger 760 is applied to input B of the NOR port 764. Output 778 of the NOR port 764 is a series of pulses that are applied to an input of the inductor discharge circuits 726, 728, 730, 732 (Figures 38, 39). A second oscillator 780 provides a clock train 782, which is applied to another input of the inductor discharge circuits 726, 728, 730, 732 (Figures 38, 39).
[00241] Figure 43 is a simplified schematic diagram of an inductor 726 discharge circuit shown in Figures 38 and 39, in accordance with an aspect of the present description. As described herein, the inductor discharge circuit 726 is coupled to the pulse generator circuit 724 (Figure 42). In this "charge pump" configuration, inductor discharge circuit 726 is applied to one of N layers of inductors. The L1 inductor section is connected in single-phase mode. As described herein, inductor section L1 includes two ports P1 and P2 for coupling inductor section L1 to corresponding circuit structures of inductor discharge circuit 726.
[00242] The inductor discharge circuit 726 comprises a capacitor charging circuit 790, a coupling circuit 792, and inductor loading and unloading circuits L1 794, 796. The inductor discharge circuit 726 receives a series pulse output 778 of the NOR port 764 (Figure 42). The pulse series is applied to a first inverter 784. Output 798 of the first inverter 784 is applied to the transistor port Q10 of the capacitor charging circuit 790, to the transistor port Q12 of the coupling circuit 792, and to the input of a second inverter 786. Output 791 of the second inverter 786 is applied to the transistor port Q9 of the capacitor charging circuit 790 and the transistor port Q11 of the coupling circuit 792. When the input to the first inverter is low, the transistors Q9 and Q10 are turned on and transistors Q11 and Q12 are turned off to charge capacitor C6. When the input to the first inverter is high, transistors Q9 and Q10 are turned off and transistors Q11 and Q12 are connected to apply voltage across capacitor C6 to input 797 of discharge circuits 794, 796.
[00243] A second oscillator 780 provides a clock train 782, which is applied to a third inverter 788. Output 793 of the third inverter 788 is applied to the ports of transistors Q13 and Q14 and the input of a fourth inverter 790. A output 795 of fourth inverter 790 is applied to the ports of transistors Q15 and Q16 so that transistors Q13, Q16 and transistors Q14, Q15 are switched on and off alternately. For example, when the input of the third inverter 788 is high, transistors Q13 and Q16 are turned on and transistors Q14 and Q15 are turned off. Thus port P1 for actuator section L1 is coupled to the capacitor voltage at input 797 through transistor Q13 and port P2 of inductor section L1 is coupled to Vss via transistor Q16. When the input to the third inverter 788 is low, the roles are reversed so that transistors Q14 and Q15 are turned on and transistors Q13 and Q16 are turned off. Thus, port P2 of inductor section L1 is coupled to the capacitor voltage at input 797 through transistor Q15 and port P2 of inductor section L1 is coupled to Vss via transistor Q14. As the pulse series arrives from output 778 of port 764 NOR (Figure 42) and train 782 from the second oscillator 780 (Figure 42), the capacitor section L1 is alternately charged and discharged to create an electromagnetic signal.
[00244] Thus, the inductor discharge circuit 726 pumps charge to capacitor C6 and then discharges capacitor C6 in inductor section L1 over a very short discharge cycle in relation to the active cycle to provide a transmission protocol. The operation of the other inductor discharge circuits 728, 730, 732 is similar to the inductor discharge circuit 726 and will not be repeated here for brevity and clarity of disclosure. IMPULSE COMMUNICATION PROTOCOLS
[00245] In some respects, a pulse communication protocol is defined to transmit a signal from the ingestible identifier (for example, ingestible identifier 104) and to be received, detected and decoded by a receiver (for example, any of the receivers 106 , 108, 110, 112, 114, 116, 118, 150, 152). Typically, the ingestible identifiers in the present descriptions are extremely small and inexpensive systems. Its cost and / or size limits the inclusion of components typically used to create a better signal quality, such as adding a crystal to the circuit to precisely tune the oscillator to a known frequency. This tends to allow the receiver to know the actual frequency of the ingestible receiver within +/- 5-10% initially. Furthermore, the bio-galvanic battery voltage and current output from an ingestible identifier tends to change across the entire transmission sequence. Due to the limited size, the signal amplitude tends to be very weak compared to any noise. Due to the very limited resources on the transmitter side (ingestible identifier), it may be desirable to use only a unidirectional communication protocol, which necessarily prevents any acknowledgment, confirmation of synchronization, or any response message from being transmitted from the receiver and received on the identifier. ingestible. Furthermore, multiple ingestible identifiers can be active on a user at the same time, each transmitting similar (and possibly different) signals that a single receiver would need to pick up before its respective battery life runs out. The system restrictions here strongly suggest that the burden to properly communicate a signal lies with the receiver, where the receiver must be configured to take into account an initially inaccurate signal frequency, a possibly changeable voltage and current output, a signal with a natively low signal-to-noise ratio, identification without any reciprocal communication, and multiple of these transmission sequences.
[00246] The aspects of the present description solve at least some of these problems, describing an impulse communication protocol that uses a series of electromagnetic pulses generated by the inductor in the ingestible identifier. These electromagnetic pulses can be transmitted according to one of the protocol variations defined below, and can be correspondingly received, detected, and decoded by the receiver according to the same protocol. The various examples of this impulse communication protocol can also be referred to here as a "peak" protocol.
[00247] In general, the peak protocol can be initiated by the impulse system of the ingestible identifier that accumulates battery charge and releases it through the inductor in a very short period, thus producing a higher signal amplitude for a longer duration shorter than that which would be obtained from a continuous wave. To produce this, the control circuit defines an interval between the pulses. Correspondingly, the receiver takes advantage of this by looking for a signal only where there should be peaks, ignoring the time between peaks. For example, if there are 10 peaks each of 1 ps duration over a period of 1000 ps, all signal energy is compressed 1% of the time. If the detector (eg, receiver) ignores the data between the pulses, then only 1% of the noise that is present during this period is actually competing with the signal energy. By comparison, in a typical "resonant system", the signal energy would be evenly distributed over the entire 1000 ps and all noise in this period would compete with the signal energy. Thus, the peak protocol can improve the signal-to-noise ratio by, in this example, 100x. The improvement of SNR is inversely related to the active cycle.
[00248] In addition, the peak protocol can allow the detection of multiple ingestible identifiers that are ingested simultaneously without interference between the signals. This is achieved because unless two signals have exactly the same frequency and transmission phase, the pulses of a coincident signal will appear in the intervals between the pulses and are thus ignored.
[00249] Figure 44 is a diagram of time and polarity 800 according to an example of the peak protocol that can be generated by the impulse inductor drive circuit 720 shown in Figures 38-43, in accordance with an aspect of the present description. The vertical geometric axis represents the voltage (V) and the horizontal geometric axis represents the "pulse delay" time (ps). The pulse function 802 comprises a series of pulses 804, 806 of different polarity over a predetermined period (~ 130 ps) or time frame. The 802 pulse function encodes the information associated with the ingestible identifier as discussed herein. Positive pulses 804 have a positive polarity or amplitude (+ 1V) and negative pulses 806 have a negative polarity or amplitude (-1V). The impulse function 802 is generated by the pulse inductor circuit 720 and is transmitted by the inductor with a transmitting antenna. The impulse or peak protocol can be biphasic or monophasic.
[00250] As described here, the transmission protocol is implemented by charging a capacitor C (for example, C6, Figure 43) and then discharging the capacitor over a very short discharge cycle relative to the active cycle in an inductor section L (for example, L1, Figure 43), as discussed in connection with the pulse inductor drive circuit 720 in Figures 38-43. The pulse protocol is a series of +/- or on / off strings in 128 locations, for example. All energy is placed in ~ 13 pulses, and the noise is distributed over 128 pulses, which improves the number of noise per bit in this example. Consequently, the peak protocol can also be referred to here as a "sparse pulse" code. An example of the impulse protocol is described here below.
[00251] Consequently, in one aspect, the "sparse impulse" code can be implemented as follows: gaps = [3 33333 333333 79]; impulseNoGapsMask = [1 -11-1-111 -1 -1 -1 -1 -1 -1 -1]; impulses = []; % load in impulse pattern for i = 1:13 a = impulseNoGapsMask (i); g = zeros (1, gaps (i)); impulses = [impulsions g a]; % variable duty cycle End code = [0 1001100011100001111001 1];
[00252] The code is the data package, it is preceded by 12 zeros (sync) and the [1 0 1 0] (preamble). The symbol definition works like this: an "impulse" (discharge from the capacitor through the coil with polarity determined by impulseNoGapsMask) is preceded by a number of non-pulses (zeros), the number coming from "intervals".
[00253] Thus the "Boost" "one" ends as 128 zeros followed by the following sequence of 128 chips: 0 0 0 1 0 0 0 -1 0 0 0 1 0 0 0 -1 0 0 0 -1 0 0 0 1 0 0 0 1 0 0 0 -1 0 0 0 -1 0 0 0 -1 0 0 0 -1 0 0 0 -1 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 -1 -1
[00254] In this definition, 128 "subchips", where a subchip is defined as either a +1 peak, a -1 peak, or no peak, make up a single chip. 64 chips make up a symbol. In this definition, there is a 1: 1 correspondence between a symbol and a bit. A zero in this case is the following sequence below, followed by 128 zeros: 0 0 0 -1 0 0 0 1 0 0 0 -1 0 0 0 1 0 0 0 1 0 0 0 -1 0 0 0 -1 0 0 0 1 0 0 0 1 0 0 0 1 0 0 0 1 0 0 0 1 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 1
[00255] In this sequence, each chip is 1 ps, each symbol and so 128 ps, and each bit is 64 * 128 = 8192 ps.
[00256] In one aspect, a "very sparse impulse" code can be used. A "very sparse pulse" code is where the interval between pulses is ~ 998 times the pulse width. This will give the ingestible handle more time for the charge pump to develop the maximum voltage on the capacitor before discharging it. This aspect will probably not vary the length of the interval between pulses, except during transitions between bits.
[00257] In one aspect, the pulses can be very short. Transmission frequencies can occur at frequencies in the range of ~ 12.5 kHz to ~ 20 kHz or greater than ~ 24 kHz and as high as ~ 10 MHz, for example. The pulses are not deterministic, but they repeat over 128 pulses at a repetition rate of ~ 6 kHz. Battery readiness is random and battery impedance (Z) and voltage (VBAT) can fluctuate. The pulse width and repetition rate can be adjusted based on the current condition of the battery. These types of protocols can be adapted to circuits of the Internet of Things type.
[00258] Figure 45 is a sparse impulse template and an 808 autoconvolution diagram of the impulse communication protocol shown in figure 44, in accordance with an aspect of the present description. The vertical geometric axis represents the voltage (V) and the horizontal geometric axis represents the "pulse delay" time (ps). A feedback pulse function 810 (shown in full line) is representative of the pulse function 802 shown in Figure 44. The auto-convolution of the feedback pulse function 810 generates an auto-convolution function 812 (shown in dashed line). The autocorrelation function 812 is the autocorrelation of the impulse function 802. The autocorrelation or autoconvolution of the impulse function 802 is a cross-correlation of the impulse function 802 with itself at different points in time. Generally speaking, it is the similarity between observations as a function of the time interval between them. The autoconvolution function 812 is a mathematical tool for finding repetitive patterns, such as the presence of a periodic signal obscured by noise, or identifying the missing fundamental frequency in a signal implied by its harmonic frequencies. This can be used by a receiver to identify the frequency of transmission or diffusion. Consequently, the pulse function 802 transmitted through space is detected by a receiver receiving antenna. The receiver includes signal processing circuits to implement functions to identify the transmission frequency of the 802 pulse function. The receiver is configured to determine the transmission frequency using the feedback pulse function 810, as well as the autoconvolution function 812 ( or autocorrelation) of the 810 feedback pulse function.
[00259] Figure 46 is a variable template diagram 814 that can be used to identify the transmission frequency of the pulse function 802 shown in Figure 44, in accordance with an aspect of the present description. The vertical geometric axis represents the voltage (V) and the horizontal geometric axis represents the "pulse delay" time (ps). The template diagram 814 shows the variable templates 816, 818, 820, 822 for the lowest transmission frequencies (template 816) to the highest (template 822) used to transmit the 802 pulse function.
[00260] According to some aspects, a peak protocol definition uses two sparse pulse sequences, here referred to as a "zero" chip and a "one" chip. Referring to Figure 62, graph 1800 shows an example of the "zero" chip pulse sequence, and graph 1810 shows an example of the "one" chip pulse sequence. Note that the zero is different than the one, and there is a phase shift from one to the other. For the chip definitions shown, available operations include calculating the autocorrelations and cross-correlations of the chips: 0x0, 1x1, 0x1, 1x0, (0 + 1) x (0 + 1). Note that in this scheme, the correlations (0x1) and (1x0) are not as important as in other protocols that do not combine all the chips to determine the alignment of the starting frame. Since this protocol uses all available data to determine the starting point, only the combined convolution (0 + 1) x (0 + 1) is important. Ideally, this convolution would have the maximum value in precise alignment and zero anywhere else. This set of specific chip definitions does not accomplish this, but it does provide a convolution where the "side lobes" are relatively small and the largest of the side lobes are of opposite polarity and conveniently located near the peak. These lateral lobes can also help to establish the "best guess" alignment.
[00261] Figure 63 shows an 1820 graph of combined data (0 + 1) correlated with a template, which illustrates how both frequency and alignment are found: the highest peak determines both. This is a relatively high case of SNR. It should also be noted that these two chip definitions produce the combined convolution only if there is an equal number of zeros and ones in the data packet. This is because the chip definitions do not have an equal number of up and down peaks in these.
[00262] To decode this peak protocol, the decoder module (for example, which processes at the receiver) looks for a single packet to decode. Both the frequency and the start times of the two packages are unknown. This does this by looking in a window that is 1.5x the maximum packet size (since it is not known where the registration packet is within the frame, so this ensures that a complete packet is obtained), and then incrementing the window by 0.5x the package distance, according to some aspects. The data for each of these thirds can be reused, so that each table actually analyzes one third of the data, keeping 2/3 of the data from the previous analysis.
[00263] In some respects, the analog data of the ingestible identifier is digitized and stored in data frames that are equal to the maximum packet length (lowest transmission frequency). Two of these frames are analyzed at a time, and the analysis information for each frame is stored and reused when the next frame is added.
[00264] To decode the packet, it is necessary to find the precise time between these pulses, and also the starting point of the communication. Thus, the pulse pattern is designed so that if the assumed time between the pulses is correct and the assumed starting point is correct, the corresponding correlation product will be very large compared to if any of them are switched off, even for a small amount. So, referring back to Figure 56, graph 1200 shows the correlation product (autocorrelation) for the best guess starting point for a variety of pulse time variations. Note the wide range of pulse time variation (0 - 1000 ps is the nominal variation, really +/- 500 ps).
[00265] Hence, to find the "best guess starting point" for each of these impulse time variations in a computationally efficient way, the first step, for each impulse time assumption, is to perform a "Distension" process or Compression "of the sampled points in a nominal frame (ie, predefined reference quantity) of a nominal number of sample points. Thus, if the time between pulses is less than the nominal, the sampled points for each set of, say, 13 peaks, must be "stretched" to the number of sample points that would represent the nominal time between the peaks. On the other hand, if the time between the peaks is greater than the nominal, then the number of samples needed to collect all 13 peaks is greater than the nominal, and the data needs to be "compressed" for the nominal number of peaks. sample. This "stretching and compression" must be done in a way that the starting point of the communication package is still unknown, but is preserved in the "stretched / compressed" data. A more detailed example to perform this stretching and compression operation is defined below in the second definition of exemplary peak protocol.
[00266] Next: the communication packet can be, for example, 40 bits long, and each bit can be represented by, for example, 64 identical chips per symbol, and each chip can be represented by, for example, 13 spikes. Thus, this definition would need a little more than 40 * 64 = 2560 "frames", where each frame represents 13 peaks (and the intervals between them). More than the number of frames must be obtained because it is not known where the package starts at this point. The more a little depends on the higher level protocol: how long between packets Typically, an interval between packets is desired to be at least a couple of bits wide so that when the decoding process starts looking for the beginning of the packet, these intervals appear as empty.
[00267] The next step in the process is to take all 2560 (in this example) frames, stack them, and add them together (the 12 data points of each of the 2560 frames are added together to make the 1- data point of the added frame, the 22 data point of each frame are added together to make the 22 data point of the added frame, and so on). This is an example of the "stack and add" operation briefly mentioned earlier. This stacking and adding operation reinforces the peaks and averages the noise.
[00268] Thus, all 2560 x 13 = 33,280 peaks are represented by a nominal size data frame. With this chart, the starting point now needs to be determined, within the chart, for the beginning of each symbol and, simultaneously, the best guess of the time between symbols. Thus, the choice of symbols for "zero" and "one" serves two important roles: For when decoding the signal, it is optimally useful to be able to distinguish between a "one" and a "zero". This is similar to pre-existing protocols. What is new here, is that when the 26 peaks that represent all the ones and zeros of the entire transmission are combined into a single frame, these should produce a template that allows for optimal identification of the starting point within the frame and real time between the peaks (ie the frequency of transmission). Figure 57 shows an example of such a section of symbols for "one" and "zero". The vertical geometric axis represents the voltage (V) and the horizontal geometric axis represents the "pulse delay" time (ps). The pulse function 1302 comprises a series of pulses 1304, 1306 of different polarity over a predetermined period or time frame. The pulse function 1302 encodes the information associated with the ingestible identifier as discussed herein. Positive pulses 1304 have a positive polarity (+0.5 V) or amplitude and negative pulses 1306 have a negative polarity or amplitude (- 0.5 V). The pulse function 1302 is generated by the pulse inductor circuit 720 and is transmitted by the inductor acting as a transmitting antenna. The impulse protocol can be biphasic or monophasic.
[00269] A first pattern or series of pulses of pulse function 1302 represents logic 0 and a second pattern or series of pulses represents logic 1. Two of pulses 1308, 1310 are twice the amplitude of the other pulses 1304, 1306 because these are common for logic 0 and logic 1. On the receiver side, the transmission frequency is unknown and the time between pulses is also unknown. The receiver first identifies the transmission frequency and then identifies the bits (logic 1 and 0) correlating through 1000 points. The receiver then compares the series of pulses received, such as the pulse function 1302 and stretches and compresses a template until there is a match between the frequency and the starting point of a packet. Thus, the receiver looks for a specific pulse function 1302 or series of pulses and correlates through many points (for example, 1000 points) in the correct offset. Logics 1 and 0 are orthogonal and slightly overlap, which allows the receiver to identify the frequency and polarity of the impulses.
[00270] Note that as both the "one" symbol and the "zero" symbol each have a peak in the 4- and 5- time slits, the amplitude of these peaks is twice that of the rest, the which are present in one comment or the other. These "double peaks" thus allow to establish the parity of the signal as received.
[00271] A next step is to perform a convolution operation to generate another graph based on a transformation of the data. As shown in Figure 59, as the summed frame data is converted to the combined peak template, the highest peak is found when there is perfect alignment, and the "side lobes" are much lower in amplitude. Figure 59 is a graphical representation of a noise-free autoconvolution of the added frame template to illustrate the relative amplitude of the lateral lobes to the main lobe. The vertical geometric axis represents the voltage (V) and the horizontal geometric axis represents the "pulse time" time (ps). The pulse function 1502 received by the receiver comprises a series of pulses 1502 of different polarity over a predetermined period or time frame. The pulse function 1502 encodes the information associated with the ingestible identifier as discussed herein. Positive pulses 1404 have a positive polarity or amplitude (+ 0.5 V) and negative pulses 1406 have a negative polarity or amplitude (- 0.5 V). The pulse function 1502 is generated by the pulse inductor circuit 720 and is transmitted by the inductor acting as a transmitting antenna. The impulse protocol can be biphasic or monophasic. The reference pulse 1504 has a much higher amplitude than the pulse series of the pulse function 1502. Figure 58 is a graphical representation of the frames added together for the best guess frequency in the presence of noise whose maximum noise amplitude is 1000x higher than the maximum amplitude of each peak. This can be generated by the receiver circuits 900 (Figure 47), 930 (Figure 49), 950 (Figure 50), 960 (Figure 51), 970 (Figure 52), 990 (Figure 53), 1010 (Figure 54), 1100 (Figure 55), according to an aspect of the present description. The vertical geometric axis represents the voltage (V) and the horizontal geometric axis represents the "pulse delay" time (ps). The pulse function 1402 received by the receiver comprises a series of pulses 1404, 1406 of different polarity over a predetermined period or time frame. Pulse function 1402 encodes the information associated with the ingestible identifier as discussed herein. Positive pulses 1404 have a positive polarity or amplitude (+ 0.5 V) and negative pulses 1406 have a negative polarity or amplitude (- 0.5 V). The pulse function 1402 is generated by the pulse inductor circuit 720 and is transmitted by the inductor acting as a transmitting antenna. The impulse protocol can be biphasic or monophasic.
[00272] A first pattern or series of pulses of impulse function 1402 represents logic 0 and a second pattern or series of pulses represents logic 1. Pulse 1410 is twice the amplitude of the other pulses 1404, 1406 because this common for logic 0 and logic 1 and is the reference impulse for a new package. On the receiver side, the transmission frequency is unknown and the time between pulses is also unknown. The receiver first identifies the transmission frequency and then identifies the bits (logic 1 and 0), correlating through 1000 points. The receiver then compares the series of pulses received such as pulse function 1402 and stretches and compresses a template until there is a match between the frequency and the starting point of a packet. Thus, the receiver looks for a specific pulse function 1402 or series of pulses and correlates through many points (for example, 1000 points) in the correct offset. Logics 1 and 0 are orthogonal and slightly overlap, allowing the receiver to identify the frequency and polarity of the pulses.
[00273] When this summed frame is convolved with the added frames template, the result was the maximum peak shown in Figure 56. The vertical geometric axis represents the voltage (mV) and the horizontal geometric axis represents the "pulse timing" time "(ps). As described here, the transmission protocol is implemented by charging a capacitor C (for example, C6, Figure 43) and then discharging the capacitor over a very short discharge cycle in relation to the active cycle in an L inductor section (for example, L1, Figure 43), as discussed in connection with the pulse inductor drive circuit 720 in Figures 38-43. The pulse protocol is a series of +/- or on / off strings in 128 locations, for example. All the energy is placed in a plurality of pulses, and the noise is distributed over a greater number of pulses, which improves the number of noise per bit. Consequently, the pulse protocol is referred to here as a "sparse pulse" code.
[00274] Returning to Figure 56, it is clear that the frequency was found within the resolution of this research. To better resolve the frequency and the starting point within the frame and also the data package within the data stream, the search process can be repeated with a finer granularity around the discovered peak, always maintaining the combination with the product highest correlation. The result of this for the noisy example is shown in Figure 61.
[00275] Once the experience and the starting point (of the package and within the frame) are known, in this example, 64 slices per bit are each added together, and then each bit length frame is then resolved at the point appropriate starting point with the "zero" template and the "one" template. (Note again that these templates are> 75% zeros, since for this protocol, in the combined slice there is a peak every 4 feet approximately 1 foot wide - which eliminates noise between the peaks to interfere with the interpretation). The higher value of the two declares the bit.
[00276] Figure 60 shows the output of each bit length frame and corresponding bit pattern of the packet using the same data as shown in Figures 56, 58, and 61. Shown is a 40-bit packet 1600 received by the circuits receiver 900 (Figure 47), 930 (Figure 49), 950 (Figure 50), 960 (Figure 51), 970 (Figure 52), 990 (Figure 53), 1010 (Figure 54), 1100 (Figure 55), according to one aspect of the present description. The vertical geometric axis represents the voltage (V) and the horizontal geometric axis represents the "pulse delay" time (ps). Despite the high noise level compared to the signal amplitude, the data is clearly and easily read.
[00277] Figure 61 is a thin spectrum of a 1700 packet received by receiver circuits 900 (Figure 47), 930 (Figure 49), 950 (Figure 50), 960 (Figure 51), 970 (Figure 52), 990 ( Figure 53), 1010 (Figure 54), 1100 (Figure 55), in accordance with an aspect of the present description. The vertical geometric axis represents the voltage (mV) and the horizontal geometric axis represents the "pulse delay" time (ps).
[00278] In another aspect, a second definition of peak protocol is presented here. Compared to the previous protocol, this second protocol definition doubles the amount of time available for the transmitter to charge the capacitor, essentially doubling the amplitude of the transmitted peak. Second, this second protocol perfects the pseudo-random code that is used to find the frequency so that the "side lobes" are all or zero or less one. Third, this code is designed to work equally well if the package is all zeros, all ones, or anywhere in between. Otherwise, this second protocol definition works in a similar way to the previous version.
[00279] In this second exemplary peak protocol definition, two "subchips" "A" and "B" are defined that can be combined in certain modes to form the "zero" and the "one" chip. Here is an exemplary definition:
[00280] Subchip definitions: The "A" subchip is {1 0 -1 0 -1 0 1 0 1 0 -1 0 1 0 -1 0 1 0 1 0 1 0 1} The "B" subchip is {0 -1 0 -1 0 -1 0 -1 0 -1 0 1 0 -1 0 1 0 -1 0 -1 0 1 0} The "zero" chip is {AB} The "one" chip is {BA} When decoding, the "stacking" length is len (A) = len (B)
[00281] The aforementioned sequences have been selected so that when they are combined, that is,
[00282] A + B = {1 -1 -1 -1 -1 -1 1 -1 1 -1 -1 1 1 -1 -1 1 1 -1 1 -1 1 1 1}
[00283] {A + B} x {A + B} produces a pattern (autocorrelation) that has a central peak 23 units high and all other lateral lobes = -1 (see Figure 68). Other codes of different length can be used, too, and aspects are not so limited. For example, at 19 length units, the code is {1 -1 -1 -1 - 1 1 -1 1 -1 1 1 1 1 -1 -1 1 -1 -1 1}. In general, the two subchip definitions can have different patterns, as long as the autocorrelation of their summation produces a pattern with a central peak equal to the length of the subchips, and the lateral lobes are not equal to 1.
[00284] Still in this definition:
[00285] 40-bit packet = 24-bit data preceded by a 16-bit preamble: preamble = [1111100110101101];
[00286] In addition, 70 chips in a row make a symbol, which is identical to the bit. (In other protocols, symbols do not have a one-to-one relationship with bits). Increasing the number of chips per symbol uses more time (packet is longer) but if the transmission clock is stable, then there is more power in each symbol and thus a lower bit error rate.
[00287] Still in this definition: 12 + 11 = 23 peaks per chip
[00288] 2 x 4 = 8 feet between peaks (except when transitioning from bit = 1 to bit = O). When the subchip frames are stacked, there will be 4 feet between 23 peaks.
[00289] 23 x 2 x 4 = 184 ps / chip
[00290] 70 chips / bit
[00291] subchip peaks "A" are spaced at 8 ps starting at t = 0;
[00292] subchip peaks "B" are spaced at 8 ps starting at t = 4 ps;
[00293] 12.88 ms / bit
[00294] 40 bits / packet, data load = 24 bits
[00295] 515.2 ms / pack
[00296] Figure 64 shows graphical representations of subchip "A" in graph 1830, and subchip "B" in graph 1840. The x-axis is the sample number, assuming 8 ps between peaks and sampling rate = 10 MSPS ).
[00297] Referring to Figure 65, based on the aforementioned exemplary definition of the second peak protocol, combining A and B according to the above descriptions produces the "Zero" = [AB] chip, as shown in graph 1850, and the chip "Um" = [BA], as shown in graph 1860.
[00298] To make a "zero" bit, 70 "zero" chips are transmitted in sequence; to make a "one" bit, 70 "one" chips are transmitted in sequence. In this mode, the entire packet is transmitted. According to some current specifications of the ingestible identifier, nominally, it takes 12.88 ms to transmit each bit and 515.2 ms to transmit a packet. At a lower transmission frequency, say, 5% lower, it may take 541 ms to transmit a packet, but at a higher frequency, say, 5% higher, only 489 ms.
[00299] When decoding the signal, enough data is stored in a frame to be sure to capture from a packet, but not so much that the noise between packets overwhelms the signal. A few empty bits of packet intervals may be sufficient, specifically if the packets are synchronized with each other.
[00300] The data is then "sliced" into segments of length equal to a subchip. However, as the transmission frequency is not exactly known, the exact length of a subchip is not known, either. The frequency range that determines the number of samples or subsamples per slice depends on the assumed transmission frequency. Thus, at nominal frequency, there may be 1840 samples per subchip = 1840 samples per slice. At a slightly lower frequency, there may be 1840.1 samples per slice, which means that for every ten slices an extra sample has been "compressed" within the slice. At a slightly higher frequency, there may be 1839.99 samples per slice, which means that for every 100 slices, one sample has been "stretched". By proper stretching and compression, slices of equal length for all frequencies are obtained. These slices can then be treated equally, without worrying about how many samples and subsamples were used to create each slice. This action is the stretching - compression slicing process. To perform the stretching - compression efficiently, a template is made which stores a network of pointers that describes the starting point for each slice in the frame for each frequency. The term template refers to a specific and predetermined pulse pattern (or pointers, slices, etc.) that acts as a reference against which to compare. Alternatively, depending on implementation restrictions, an algorithm could be used to continuously generate each template.
[00301] The slices are then stacked and added. Since each slice in this example has 1840 samples, the 1- sample from the 1 slice is added to the 1 st sample from the 2 nd slice, and then the 1 st sample from the 3 slice is added to this sum, and so on until all the first samples of all slices are added to the first sample of the combined slice. In this mode, all 1840 samples from the combined slice are produced, each adding up to the same number of samples on each of all slices.
[00302] Without noise, this combined slice can look like the graph shown in Figure 66. This combined slice can have an SNR = 5000.
[00303] Adding the subchip "A" and the subchip "B" produces the "template", which is used in decoding to find the correct frequency and starting point of the package. The template is shown in Figure 67. Note that the spacing between the 23 peaks is 40 samples or 4 ps. As there is always an equal number of A and B chips, the amplitude of sums is always nominally equal (the noise will cause these amplitudes to vary in practice).
[00304] The next step is to convolve the combined slice with the combined slice template to find the best coincident starting point for each assumed frequency. A typical low-noise convolution for the best matching combined slice (matching the combined slice shown above) is shown in Figure 68. This graph shows the sum of template convolution versus slice number.
[00305] Note that when the template aligns with the best-adjusted combined slice, the amplitude is 23. When the slice is misaligned by the equivalent of 4 ps, the amplitude is -1. In all other misalignments, the amplitude is zero. Two values are retained for each assumed frequency: peak amplitude and sample number. Note that the absolute value of this correlation score is compared with the others. If the best-fit score is negative, then each data point in the data set is multiplied by -1 in successive calculations.
[00306] The maximum convolution value for each assumed frequency is calculated, and stored. A graph of these values versus assumed frequency is the "spectrum". Shown in Figure 69 is the spectrum for this example of SNR = 5000: (best sum of convolution versus "frequency").
[00307] This example shows that the frequency is close to the nominal value, which would be 501. If the peak is closer to 1, then the frequency is below the nominal (for example, nominal length - 1); if it is closer to 1000, then the frequency is above the nominal (for example, nominal length + 1). From the highest peak, we learned two things: the actual transmission frequency and the starting index (from the previous graph in Figure 68) within the combined slice.
[00308] The next step is to produce (or remove from memory) the pointers to this frequency and its starting index. Pointers are a list of numbers, each representing a starting point and template for each slice.
[00309] The pointers and template are then used to generate two subfile scores for each slice: a subchip score "A" and a subchip score "B".
[00310] Shown in Figure 70 are the subchip scores "A" for each slice for the case of very low noise: (geometric axis X: slice number, geometric axis Y: correlation value). Note that as there is very little noise in this example, the beginning and end of the package are very easy to see. Magnifying the beginning of the package, the chip A score is shown in Figure 71: (geometric axis X: number of slice, geometric axis Y: correlation for "template A" value).
[00311] Plotting both the subchip A and subchip B correlation values together is shown in Figure 72. It is easy to see that when the subchip A score is high, the subchip B score is low, and vice versa. Note that the score for subchip A is higher than the score for subchip B in this example. This is because there is more of a peak in subchip A than in subchip B, producing a "combined" chip (when stacked together), which is an odd number, thus allowing all -1 side lobes to be as shown in the combined slice of best fit of Figure 68 above.
[00312] The next step is to generate, using the subchip scores, "zero" and "one" chip scores for each slice. Here is the formula, according to some aspects: for subChipNum = 1: chipsPerFrame chipScores (subChipNum, 1) = subChipScores (subChipNum, 1) + subChipScores (subChipNum + 1,2); chipScores (subChipNum, 2) = subChipScores (subChipNum, 2) + subChipScores (subChipNum + 1,1); end chipScores (:, 3) = chipScores (:, 2) -chipScores (:, 1); % Use for decoding chipScores (:, 4) = chipScores (:, 2) + chipScores (:, 1); % Use for finding the packet start & finish
[00313] Thus, a "zero" chip is the sum of subchip A (n) + subchip B (n + 1), while the "one" chip is the sum of subchip B (n) + subchip A (n + 1 ). Note that the difference between the zero chip and chip one scores is used for decoding, while the sum of the two is used to find the packet starting point.
[00314] Figure 73 shows a graph of the "zero" chip values as a function of slice number.
[00315] Figure 74 shows a graph of chip scores both zero and one as a slice number function. Again, note that when one chip's score is high, the other is low. Registering, that is, determining the exact starting point of the package, is critical here: if one is out for a slice, all zero chips become ones, and vice versa. This problem is solved by starting the packet with a known bit stream, the "preamble".
[00316] The next step in decoding is to calculate for each slice number two "bit scores", one adding all zero subchips for each bit length of subchips, the other adding all subchips for each bit length of a subchip . The MATLAB code for this is shown below as an example of how to implement this step: bitLengthScores (1: chipsPerFrame-subChipsPerBit, 1: 2) = 0.0; for chipNum = 1: chipsPerFrame - subChipsPerBit for thisChipNum = chipNum: 2: chipNum + subChipsPerBit-1 bitLengthScores (chipNum, 1) = bitLengthScores (chipNum, 1) + chipScores (thisChipNum, 3); bitLengthScores (chipNum, 2) = bitLengthScores (chipNum, 2) + chipScores (thisChipNum, 4); end end
[00317] Note that two bit length scores are produced: one using the difference of the chip scores, and the second based on the sum of the chip scores. The latter becomes the package envelope. To be sure, a table as used here represents a segment of data being analyzed, which must contain a packet. Thus, in a frame, the package would be surrounded by noise.
[00318] Figure 75 shows a graph of bit length versus slice number scores. Note that although the second bit length score represents the envelope of the bit length scores used to decode the packet, the bit length score turns with each slice number. The exact starting point is found using an algorithm that rewards starting points that produce the correct preamble, while giving credit to slices that have valid bits. Thus, a combination of the first bit length score (for the preamble bits) and the second bit length score (for the data packet bits) is used to find the best estimate of the packet.
[00319] An exemplary MATLAB code to search through the slices to make this calculation is shown below: preamble = params, preamble * 2-1; bestSC (1: 2) = 0.0; thisPacket (1: 40,1: 3) = 0.0; bestPacket (1: 40,1: 2) = 0.0; for chipNum = 1: chipsPerFrame - subChipsPerPacket for i = 1:40 thisPacket (i, 1) = bitLengthScores (chipNum + (i- 1) * subChipsPerBit, 1); thisPacket (i, 3) = bitLengthScores (chipNum + (i- 1) * subChipsPerBit, 2); if thisPacket (i, 1)> 0 thisPacket (i, 2) = 1; else thisPacket (i, 2) = 0; end end thisPreamble = thisPacket (1: 16,1). * preamble; thisScore = 0.0; factor = 1.0; for preambleNum = 1:16 if thisPreamble (preambleNum)> 0 factor = factor * 1.01; else factor = 1.0; end thisScore = thisScore + factor * thisPreamble (preambleNum); end thisScore = thisScore + sum (thisPacket (17: 40,3)); if thisScore> bestSC (2) bestSC (1: 2) = [chipNum thisScore]; bestPacket (:, 1: 2) = thisPacket (:, 1: 2); endend
[00320] bestPacket (:, 1) bestPacket (:, 1) / max (bestPacket (:, 1));
[00321] At this point, the best estimate of the package has been determined. The preamble is checked to see if it is correct. If it is correct, then the data load is recorded, and assumed to be correct. Depending on the signal's SNR (see below), a number of data packets on the same or similar frequency are determined and if they match, then the data packet is assumed to be correct. Alternatively, if the SNR is below a certain number, a number of these bit length scores can be combined to produce a metabit length score that combines neighboring data packets to produce a better estimate of a single data packet.
[00322] Figure 76 shows a graph of the low noise package. Two lines are shown: the first line that falls the deepest is the bit length score and the shallowest line is the bit value as interpreted. Now, you can see what these same parameters look like in the presence of various amounts of noise. In all the following examples, SNR is measured to be Vmax / V rms noise, where Vmax is the peak amplitude and V rms noise = sqrt (mean (noise. * Noise)) (MATLAB notation). Here is the relevant MATLAB code that illustrates this: noise = 2.0 * rand (1, length (signal)) - 1.0; noiseRMS = sqrt (mean (noise. * noise)); vMax = 000.0192; inData = 1.0 * signal * vMax / max (signal); log_vMaxOverVn = 10.0 * log (vMax / noiseRMS) yesData = inData + noise;
[00323] Figure 77 shows four graphs of the combined slice best adjusted in different signal to noise ratios. Graph 1900 shows the combined slice best adjusted for SNR = 5 dB. Graph 1910 shows the combined slice best adjusted for SNR = - 15 dB. Graph 1920 shows the combined slice best adjusted for SNR = -24 dB. Graph 1930 shows the combined slice best adjusted for SNR = -34 dB.
[00324] The next critical parameter is produced by converting the "best-adjusted sums" into the template to determine the starting point of the best guess within the combined sum.
[00325] Figure 78 shows multiple graphs of the "bestThisSums", which is the "best adjusted sums" converted with the "template" for several SNRs. In each case, the graph is the "best guess", that is, the frequency that produced the maximum peak. Graph 2000 shows this convolution of "bestThisSums" to SNR = 5 dB. Each frequency will produce a peak: the highest peak is the correct frequency (see "spectrum" for a graph of the peaks for each frequency). The peak location (the highest total peak) indicates the starting index. Thus, when the table is broken into slices, this starting index is used to correlate the subchip A and subchip B templates to produce subchip scores for each slice. It could also be said that the location of the peak decides to record the starting point of each subchip within each slice.
[00326] The 2010 chart shows the "bestThisSums" for SNR = -15 dB. The 2020 chart shows the "bestThisSums" for SNR = -24 dB. Graph 2030 shows the "bestThisSums" for SNR = -34 dB. Note that even in the case of -34 dB (which represents a data set where the peak amplitude of the peaks is ~ 2% of the peak amplitude of the background noise), the correlation values are still easily found. In this case, the correct peak (~ 3000) is approximately three times that of the next closest peak (~ -1000).
[00327] Plotting the best correlation values bestThisSums for each frequency produces something similar to a "spectrum", that is, the best adjusted correlation versus frequency number. Figure 79 shows several spectrum graphs in different SNR. Graph 2100 shows the spectrum for SNR = 5 dB. Graph 2110 shows the spectrum for SNR = -15 dB. Graph 2120 shows the spectrum for SNR = -24 dB. At -24 dB, the peak amplitude is ~ 5% of the peak noise amplitude. The ratio of best peak correlation to next best peak is ~ 7. Graph 2130 shows the spectrum for SNR = -34 dB. This signal is decoded with very high accuracy even at this noise level.
[00328] Again, at the point where the detection accuracy of a single packet begins to slide significantly, the peak is ~ 3x that of the next largest peak. Once this ratio falls below 4 or 5, it might be useful to start combining packets at both the spectrum level (to see if the peak-to-noise ratio is better than ~ 5) and the bit length punctuation level to improve decoding accuracy.
[00329] The bit length scores used to successfully decode the packet at these various SNR levels are shown in Figure 80. Graph 2200 shows the bit scores for SNR = 5 dB. Graph 2210 shows the bit scores for SNR = -15 dB. Graph 2220 shows the bit scores for SNR = -24 dB. Graph 2230 shows the bit scores for SNR = -34 dB. Graph 2230, where SNR = -33.9 dB, which corresponds to the peak amplitude = 1.95% of maximum noise amplitude, was successfully decoded. Either by combining packets or using more subchips per chip, signals comprised of smaller amplitude peaks in relation to background noise can be found and decoded.
[00330] In the definition of the third example of the peak protocol, instead of using only 2 subchips, N orthogonal chips, where N is the number of predefined units on each chip itself, can be used to be combined in a number of ways widely bigger. In this case, N = 23, but other sizes can be used (for example, N = 19 or 17). In this example, compared to the first protocols described above, this third definition increases the amount of time available for the transmitter to charge the capacitor between discharges by a factor of 23, vastly increasing the amplitude of the transmitted peak (given charging system limited to, as ingestion sensor). Second, this protocol definition enhances the pseudo-random code that is used to find the frequency so that the "side lobes" are all or zero or less one (same as in the second protocol). Third, each package is made up of the same 23 unique symbols, but the order of appearance of these 23 symbols determines the information. (The first peak protocol required an equal number of zeros and ones in the packet to work properly). Otherwise, the protocol works in a similar way as the previous revision.
[00331] Defined here are the chip definitions for this third exemplary protocol definition:% of subchip peaks "A" are over 92 psp starting at t = 0; % of subchip peaks "B" are over 92 ps spacing starting at t = 4 ps; % of subchip peaks "C" are over 92 ps spacing starting at t = 8 ps; % ...% of subchip peaks "W" are over 92 ps spacing starting at t = 88 ps; % 240 chips / symbol (for example, 240 "A" chips in a row makes an "A" symbol)% 44.16 ms / symbol% 23 symbols / package, data load = 2% 270.5 ms / package O Chip "A" is {1 000000000000000000000 0} Chip "B" is {0-1 00000000000000000000 0} Chip "C" is {0 0-1 0000000000000000000 0} Chip "D" is {0 00-1 000000000000000000 0 } The "E" chip is {0 000-1 00000000000000000 0} The "F" chip is {0 0000-1 0000000000000000 0} The "G" chip is {0 000001000000000000000 0} The "H" chip is {0 000000- 1 00000000000000 0} The "I" chip is {0 000000010000000000000 0} The "J" chip is {0 00000000-1 000000000000 0} The "K" chip is {0 000000000-1 00000000000 0} The "L" chip is { 0 000000000010000000000 0} The "M" chip is {0 000000000001000000000 0} The "N" chip is {0 000000000000-1 00000000 0} The "O" chip is {0 0000000000000-1 0000000 0} The "P" chip is { 0 000000000000001000000 0} The "Q" chip is {0 000000000000000100000 0} The "R" chip is {0 0000000000000000-1 0000 0} The "S" chip is {0 00000000000000000-1 000 0} The "T" chip is { 0 000000000000000000100 0} The "U" chip is {0 000000000000000000010 0} The "V" chip is {0 00000000000000000000-1 0} The "W" chip is {0 000000000000000000000 1}
[00332] When decoding, the "stacking" length is length (A) = length (B) = ... = length (W)
[00333] The aforementioned strings have been selected so that when the 23 symbols are combined (240 chips A make a symbol A, 240 chips B make a symbol B, etc.), that is,
[00334] {A + B + C + ... + W} = {1 -1 -1 -1 -1 -11-11-1-111 -1 -1 11-11-1111}
[00335] {sum (A: W)} x {sum (A: W)} produces a pattern (autocorrelation) that has a central peak 23 units high and all other side lobes = -1 (see Figure 68) . Other codes of different length can be used, too. For example, at 19 units in length, the code is {1 -1 -1-1-11-11-1111 1-1-11 -1 -1 1}.
[00336] One of the unique characteristics of this protocol is that the packet is composed of exactly 23 symbols, A - W. Each symbol is comprised of some sequential number of relative chips. In this situation, 240 chips per symbol produce a package whose duration is similar to previous protocols. Using more chips per symbol increases the amplitude of each symbol when the chips are added, and is the average time of most noise, reducing its average magnitude.) The information is contained in the order in which the symbols appear. So there are 23! (23 factorial) equal to ~ 1021 unique codes, approximately 70 bits of information. These "bits" are used for the preamble of packet, address, and data, and other purposes. For example: preamble = AFKPT ID: 000 = BC DE GH IJ LM NO QR SU VW ID: 001 = BC DE GH IJ LM NO QR SU WV ID: 010 = BC DE GH IJ LM NO QR SV UW ID: 011 = BC GH IJ LM NO QR SV WU ID: 100 = BC GH IJ LM NO QR SW UV ID: 101 = BC GH IJ LM NO QR SW VU
[00337] Below are definitions for this subchip, chip, symbol and bits protocol:
[00338] There are 23 subchips per chip (the same as the number of peaks in the template). Each subchip is in an equally spaced location for a peak to occur; a peak can be +1 or -1.
[00339] There are 240 chips per symbol (it could be more or less, too).
[00340] There are 23 unique symbols per package.
[00341] The relationship between symbols and bits is a more complicated one and depends on how many symbols, if any in each case, are used for the preamble, the address, and the data field.
[00342] For example, to provide the above preamble and address = binary (101), the package would be simply:
[00343] Package = {AFKPTBCDEGHIJLMNOQRSWVU}
[00344] Increasing the number of chips per symbol is more time consuming (the packet is longer) but if the transmission clock is stable, then there is more power within each symbol and thus a lower bit error rate. It will be discussed how the peak slice algorithm can resolve frequency variations with the packet later.
[00345] Figure 81 shows the first four "A" chips. The geometric axis x is sample #, assuming 92 ps between peaks and sample rate = 10 MSPS.
[00346] Figure 82 shows a graph of the signal, as transmitted, assuming 240 chips per symbol. Note in Figure 82, the signal looks similar to the 23-bit template pattern, only that the peaks are much wider. This is because each "bit" of the 23-bit template pattern is 240 identical peaks: either all +1 or all -1.
[00347] To make an "A" symbol, 240 "A" chips are transmitted in sequence; to make a "B" symbol, 240 "B" chips are transmitted in sequence. In this mode, the entire packet is transmitted. Nominally, it takes 44.16 ms to transmit each symbol and 541 ms to transmit a packet. A lower transmission frequency, say, 5% lower, can take 568 ms to transmit a packet, but at a higher frequency, say, 5% higher, only 514 ms.
[00348] When decoding the signal, enough data is stored in a frame to be sure of capturing a packet, but not so much that the noise between the packets outweighs the signal. A few empty interval bits between the packets may be sufficient, specifically if the packets are synchronized with each other.
[00349] The data is then "sliced" into segments of length equal to a subchip. However, as the transmission frequency is not exactly known, the exact length of a subchip is not known either. The frequency range that determines the # of samples or subsamples per slice depends on the assumed transmission frequency. Thus, at nominal frequency, there may be 920 samples per chip = 920 samples per slice. At a slightly lower frequency there may be 920.1 samples per slice, which means that for every ten slices an extra sample has been "compressed" within the slice. At a slightly higher frequency, there may be 919.99 samples per slice, which means that for every 100 slices, one sample has been "stretched". By proper stretching and compression, slices of equal length for all frequencies are obtained. These slices can then be treated equally, without worrying about how many samples and subsamples were used to create each slice. This action is the stretching-compression slicing process. To perform the stretch-compression efficiently, a template is made which stores a network of pointers that describes the starting point for each slice in the frame for each frequency.
[00350] The slices are then stacked and added. Since each slice, in this example, has 920 samples, the 1st sample of the 1st slice is added to the 1 ^ sample of the 2-slice, and then the 1 ^ sample of the 3-slice is added to this sum, and so on until all the first samples of all the slices are added to the 1 ^ sample of the combined slice. In this mode, all 920 samples from the combined slice are produced, each adding up to the same number of samples on each of all slices.
[00351] Without noise, this combined slice may look like the one shown in Figure 66, which shows a combined slice with SNR = 5000. Note that the combined slice in Protocol 3 looks exactly the same as the combined slice in Protocol 2 In fact, if the duration of the packets were the same, and the amount of energy that was transmitted by the packets was the same, then the two slices combined would actually be identical. The difference is that in Protocol 3, 23 * 4 ps = 92 ps of load pumping occurs between each peak, while in Protocol 2, 2 * 4 ps = 8 ps of load pumping occurs between each peak. Thus, the amplitude of each peak in Protocol 3 is approximately ten times the amplitude of each peak in Protocol 2. Now, if the initial analog interfaces on each system were "ideal" and the analog to digital converter on each system was also "ideal" "then, with the total available energy and the number of peaks in the combined slice fixed, there would be no difference in the combined slice of Protocol 2 and Protocol 3. But the world is not ideal, and there are likely cases where a 10x increase in Peak amplitude means that the least significant bit of the ADC often turns enough during a peak, so that when 240 peaks are added for each of 23 locations in time, then a detectable set of peaks is observed. In addition, having 92 ps between peaks encourages the use of a peak slice algorithm that takes advantage of this fact and eliminates noise between these 92 ps peaks. This increases the noise contribution by approximately 99%, compared to the 75% reduction possible with Protocol 2 previously described. We will explore this variation a little later.
[00352] Adding all chips "A" to "W" produces the "template", which is used in decoding to find the correct frequency and the starting point of the package. This is the same template as used in Protocol 2 (see Figure 67).
[00353] Note that the spacing between the 23 peaks is 40 samples or 4 ps. As there is always an equal number of chips A and B, the amplitude of sums are always nominally equal (the noise will cause these amplitudes to vary in practice).
[00354] The next step is to convolve the combined slice with the combined slice template to find the best match starting point for each assumed frequency. A typical low-noise convolution for the best-matched combined slice (matching the combined slice shown above) is shown in Figure 68 again.
[00355] Note that when the template aligns with the best adjusted combined slice, the amplitude is 23. When the slice is misaligned by the equivalent of 4 ps, the amplitude is -1. In all other misalignments, the amplitude is zero. Two values are retained for each assumed frequency: peak amplitude and sample number. Note that the absolute value of this correlation score is compared with the others. If the best-adjusted score is negative, then each data point in the data set is multiplied by -1 in successive calculations. This process is identical to that of Protocol 2.
[00356] The maximum convolution value for each assumed frequency is calculated. A graph of these values versus assumed frequency is the "spectrum". See Figure 69 again for a graph of the SNR = 5000 spectrum in this example.
[00357] This example shows that the frequency is close to the nominal value, which would be 501. If the peak is closer to 1, then the frequency is below the nominal; if it is closer to 1000, then the frequency is above the nominal. From the highest peak, we learned two things: the actual transmission frequency and (from the previous graph) the starting index within the combined slice.
[00358] The next step is to produce (or remove from memory) the pointers for this frequency and this starting index. Pointers are a list of numbers, each representing a starting point and template for each slice.
[00359] The pointers and template are then used to generate 23 chip scores for each slice: an "A" chip score up to a "W" chip score. Each chip score is the correlation sum of that slice converted to the template for that chip. Thus, the template for chip "A" is a single peak in time sample number 1 (for example ...). The template for the B chip would be a single peak (ie, expected signal received in a low noise system from the capacitor discharged through the coil) at sample number 41 (ie, at = 4 ps, assuming 10A6 samples per second) .
[00360] Shown in Figure 83 are the subchip scores "A" for each slice in case of very low noise. The X axis represents the slice number, and the Y axis represents the correlation value. Note that, as there is very little noise in this example, it is easy to see that the A chips occur at the beginning of the package.
[00361] Figure 84 shows the F chip scores for each slice for the case of very low noise. Similarly, as the second symbol in the package, the F chip scores for each slice are high when the second symbol in the package would be expected to occur.
[00362] Figure 85 shows a graph of all chip scores A through W versus slice number. It is easy to see, in the case of low noise, that the values of each symbol are approximately zero whenever they are not present. This is because all chips share the same record, or starting point, and so each symbol is orthogonal to each of the other symbols, given this record. Thus, a key difference with other protocols is that all packet energy is used to find the frequency and the slice registration point. For any given registration point on the slice, all symbols are orthogonal to each other. Although it might make sense, if someone wanted, for example 140 bits of information, to simply repeat the packet of 23 symbols in a different permutation. That would work, of course, and again all the packet energy would be used to find the frequency, but now, for this amount of packet energy, the energy per symbol would be half. A better proposal to achieve the same objective would be to find a system of 25 symbols that has a similar pattern of autocorrelation. The 25-symbol pack could generate 84 bits. In this case the symbol energy / packet energy would be reduced by only 8%. Thus, each chip score has 23 numbers, each a correlation sum for a symbol for a single slice.
[00363] Finally, only one of these chip scores per slice will be used in the calculation of the best guess package. This means, that the signal in a period of ~ 1 ps is gathered together with the noise that occurs during that 1 ps. However, the noise that occurs in the other 91 feet of each slice is completely left out. An alternative modality, however, could be to average all 23 chip scores for each slice, and subtract the average from the other chip scores for each chip score. This alternative modality, however, would then gather and use noise at 22 more microseconds per slice. Perhaps there are certain situations where this can be an advantage.
[00364] In any case, the next step is to generate, using the chip scores, the symbol length scores for each slice. Again, there are 23 symbolic scores for each slice, each representing the sum of chip scores for that slice and the next 239 slices. Here is the formula: for chipNum = 1: symbolsPerFrame - chipsPerSymbol for thisChipNum = chipNum: chipNum + chipsPerSymbol for symbolNum = 1:23 symbolLengthScores (chipNum, symbolNum) = symbolLengthScores (chipNum, symbolNum) ... + chipScores (thisChipNum, symbolNum, symbolNum, symbolNum, ; end end end
[00365] Figure 86 shows a graph of each of the symbol length versus slice number scores. At this point, the next step is to determine a packet length score for each slice. To do this, you start by declaring the maximum symbol length score for each slice to be this symbol. When there is little noise, this is easy: one of the symbols has a very high score, the others have very small scores. Then, these maximum symbol length scores from the appropriate 23 time points that define a package are added together and a "package score" is determined for each slice. As you work through all the candidate slices for the highest package score, you should also check to see if the 23 symbols you choose are unique, that is, each symbol "maximizes" once and only once. As you search through the slices for the maximum package score, you can ignore most of those that are not the largest in the first cut. If the slice with the highest package score does not identify 23 unique symbols (because of noise), then an error correction algorithm is used to find the best guess package with 23 unique symbols.
[00366] One way to execute such an algorithm is shown below in the exemplary MATLAB code: symbolLen = length (allSymbolScores); packetSums (1: symbolLen, 1: 2) = 0.0; [convolutionsums, symbolNums] = sort (allSymbolScores, 1, 'descend'); [thisBestSum, thisBestSymbol] = max (convolutionSums (1,1: 23)); % Find the highest correlation value and locationamong all 23 x 23 while thisBestSum> 0.0 thisLocation = round (symbolNums (1, thisBestSymbol)); if packetSums (thisLocation, 1) <1 packetSums (thisLocation, 1: 2) = [thisBestSymbol thisBestSum]; % Store thisBestSymbol in the thisLocation symbol location and its correlation score convolutionSums (1: symbolLen, thisBestSymbol) = 0.0; % Zero out the rest of thisBestSymbol correlation scores else% IN this case, the packet location is already filled, but this symbol has not been declared. % Eliminate the found location for this symbol and shift the% values for the other locations for this symbol up. convolutionSums (1: symbolLen-1, thisBestSymbol) = convolutionSums (2: symbolLen, thisBestSymbol); symbolNums (1: symbolLen-1, thisBestSymbol) = symbolNums (2: symbolLen, thisBestSymbol); end [thisBestSum, thisBestSymbol] = max (convolutionSums (1,1: 23)); % Find the highest correlation value and locationamong all 23 x 23 end
[00367] First, the 23 symbol scores for each of the 23 package locations are stored in an array. This matrix is then classified so that the highest symbol length scores for each location are found. The high symbol length score for all locations is found, and this symbol is declared for that location. The symbol is then removed from the competition for the other 22 locations. The next highest symbol length score for the remaining 22 locations is then found and the symbol for that location is declared and that symbol is removed from the competition for all other locations. The above algorithm is a way of doing this, but there are probably other, more efficient ways to correct errors. For example, if there is a preamble, then this information can be used to find the best guess package and an estimate of the guess accuracy. Finally, if error correction is required, then the packet score for this slice number will be lower. However, it could still be the best total package score.
[00368] Thus, the best estimate of the package was determined. Depending on the SNR of the signal, a number of data packets on the same or similar frequency are determined and if they match, then the data packet is assumed to be correct. Alternatively, if the SNR is below a certain number, a number of these bit length scores can be combined to produce a meta-symbol length score that combines neighboring data packets to produce a better estimate of a single data packet.
[00369] Figure 87 is a graph showing the low noise package (-5.5 dB). Two lines are shown: the orange line 2270 that changes gradually with values just below ten is the normalized bit length score at this location and the fast changing line 2280 (blue) with values ranging from 1 to 23 is the symbol value as interpreted.
[00370] Now, it can be determined how these same parameters appear in the presence of various amounts of noise. In all of the following examples, SNR is measured to be Vmax / V rms noise, where Vmax is peak amplitude and V rms noise = sqrt (mean (noise. * Noise)) (MATLAB notation). Here is the relevant MATLAB code: noise = 2.0 * rand (1, length (signal)) - 1.0; noiseRMS = sqrt (mean (noise. * noise)); vMax = 000.0192; inData = 1.0 * signal * vMax / max (signal); log_vMaxOverVn = 10.0 * log (vMax / noiseRMS) simData = inData + noise;
[00371] In some aspects, (and alluded to earlier), an important variation for the symbol length stretching / compression process is used. In this process, the data frame is broken into slices of overlapping symbol length. Alternatively, the data frame is broken into slices of length equal to 1.5 times the symbol length, and these slices increase to 0.5 times the symbol length. In this case, sub-slices can be used over successive slice calculations to reduce computations. This variation ensures that all energy from a single symbol will be contained in a single slice. Although this process may not have much effect when finding the right frequency, it can be useful when decoding the signal. In any case, each of these slices is then stretched or compressed into a combined slice of nominal length (in this example, 920 samples in length). An example of low noise of the correct frequency is shown in Figure 88. Here, a first combined slice of the symbol length slice is shown.
[00372] Note that only one peak appears. This is because the first slice captures only part of the first symbol and none of the second symbol. The second slice overlaps the first slice by some percentage. In that case, the percentage is 50%. The purpose of this is to ensure that one of these slices captures most of the symbol information and the peak can be found.
[00373] The second combined slice sum of the symbol length slice is shown in Figure 89. Note that the same peak that appeared on the first slice (close index = 400) also appears on the second slice. In addition, part of the next symbol (close index = 200) is also seen.
[00374] Figure 90 shows two graphs of the same sum of first slice and second slice, in the presence of noise, in graphics 2270 and 2280, respectively. Graph 2270 shows the first slice of the symbol length slice with SNR = 7 dB. Note that this was a different set of data, and the peak appears over a different index of this combined slice. Similarly, graph 2280 shows the second slice of the symbol length slice, with SNR = 7 dB. Note that the two peaks are visible above the background noise in this combined slice.
[00375] As only one or at most of the peaks in each of these symbol length frames is expected to be shown, the template is that of a single peak, shown in Figure 91. Figure 91 shows the template used for the slices of symbol length. When this template is converted to the combined slice shown in the two graphs in Figure 90, the result is shown in Figure 92. Figure 92 illustrates the convolution of the combined slice shown in Graph 2270 with the template shown in Figure 91. This is analogous to result in Figure 68.
[00376] Figure 93 shows the convolution of the combined slice shown in Graph 2280 with the template shown in Figure 91. This is analogous to the result in Figure 68.
[00377] In this variation of slice compression / stretching, two peaks are expected to be seen. These two peaks are the only information ideally to be collected, and the rest can be disregarded, which is just noise. In this mode - by eliminating noise where there is no signal - the signal for total system noise can be improved. In fact, using only one of these peak values in later calculations, approximately 98% of the noise present during transmission is eliminated from the analysis. So it is for each symbol length slice:
[00378] A data symbol length of 1.5x is compressed / stretched into a slice of nominal length (in this case 920 data points) (1.5x is used to ensure that each of each peak is in a combined slice) ;
[00379] The combined slice is convolved with a template consisting of a single peak.
[00380] The two upper peaks resulting from the convolution that are at least 35 feet apart are stored in memory together with their indexes (the index and magnitude are both maintained). The sum of the absolute values of each of the two peaks is added to a variable called Spectrum (frequency). Thus, each of the magnitudes (absolute values) of the two upper peaks in each of the symbol length slices are added together to make the value that is compared with that of all other frequencies to find the correct frequency. These spectrum values can be plotted as a function of frequency, as shown in Figure 94 for the same noise case. Figure 94 shows the spectrum: the sum of the magnitudes of the two peaks for each of the symbol length slices has a frequency function. This is analogous to Figure 69.
[00381] Note that compared to Figure 69, this peak in spectrum is much wider and smoother. This is because as only one symbol at a time is being analyzed, the filtering has a wider bandwidth. (Part of the smoothness is due to the fact that only magnitudes are plotted here; the previous spectrum graphs included the data set parity). There is a lack of specificity in all frame strain / compression analysis with a 23-peak template. On the other hand, a large amount of noise was eliminated from the analysis. In the 23-peak template, each peak is approximately 1 foot wide over a 4 foot spacing. Between the peaks the value of the template is zero. Thus, with each convolution, 75% of the noise is eliminated - the spaces between the peaks in the template. In the proposed length / compression of symbol length, however, the template is a single peak 1 ps wide, and is used twice. In this case, 2 ps of noise is included and 90 ps or 98% of the noise is eliminated.
[00382] To see how this benefits the discovery of the frequency when the noise level is even higher, shown in Figure 95 are the spectra for both the frame length strain / compression analysis and the length strain / compression analysis symbol.
[00383] Graph 2300 of Figure 95 shows the spectrum of the frame length slices as a function of frequency. SNR = - 10.6 dB. This was computed using the identical algorithm used to generate the graph in Figure 69.
[00384] Graph 2310 of Figure 95 shows the spectrum of symbol length slices as a function of frequency. SNR = - 10.6 dB. This was computed using the identical algorithm used to generate the graph in Figure 94.
[00385] Note that in the above comparison, the correct answer (index = 501) is produced. It is clear, however, that the peak on chart 2330 is a smoother curve, and there is more certainty that a signal is present.
[00386] Shown in Figure 96 are the results of a noisier run. Graph 2320 shows the spectrum for the frame length slices as a function of frequency. SNR = - 13.5 dB. This was computed using the identical algorithm used to generate the graph in Figure 69.
[00387] Graph 2330 shows the spectrum for the symbol length slices as a function of frequency. SNR = - 13.5 dB, but with only 120 chips per symbol. This was computed using the identical algorithm used to generate the graph in Figure 94.
[00388] Note that in the case of frame length, the correct answer (501) appears in third place, after the peaks close to the 600 and 520 indices. This package, therefore, has not been successfully decoded. The spectrum based on the symbol length of symbol length slices in graph 2330, however, found the correct frequency, exactly.
[00389] Referring to Figure 97, shown in graph 2340 is the spectrum for the frame length slices as a frequency function. SNR = -17.5 dB, but with only 120 chips per symbol. This was computed using the identical algorithm used to generate the graph in Figure 69.
[00390] Graph 2350 shows the spectrum for the symbol length slices as a function of frequency. SNR = - 17.5 dB, but with 120 chips per symbol. This was computed using the identical algorithm used to generate the graph in Figure 94.
[00391] When the SNR was further decreased, the spectrum based on frame length slices in graph 2340 did not come close to identifying the correct frequency. On the other hand, the spectrum based on the symbol length slices, in graph 2350, estimated the frequency to be 505 units instead of target 501, close enough to successfully decode the package.
[00392] To see how this works at a more granular level, shown in graph 2360 of Figure 98 are the same 2-slice, same data set as in graph 2280 (see Figure 90), but at a frequency that is 10 units higher. In graphic 2360, shown is the second slice of the symbol length slice, with SNR = 7 dB, but the frequency is in 511 units instead of 501. It is noted that most of the information contained in the peak is retained. The peak is only slightly lower.
[00393] Shown in graph 2370 is the second slice of the symbol length slice, with SNR = 7 dB, but the frequency is at 521 units instead of 501. Based on this, it can be easily seen as extending the peaks over more indices, the magnitude of the peak is reduced. This is almost imperceptible when the search frequency is out by 10 units, but more obvious when it is out by 20 units.
[00394] Referring to Figure 99, shown in graph 2380 is the second slice of the symbol length slice, with SNR = 7 dB, but the frequency is in 551 units instead of 501.
[00395] In graph 2390, shown is the second slice of the symbol length slice, with SNR = 7 dB, but the frequency is at 571 units instead of 501. Note that when the frequency is off by 70 units, the magnitudes of the peaks are approximately half of what they were when the frequency was exactly correct.
[00396] It should be noted here that instead of allowing all 23 symbols to be randomly placed inside the package to produce 23! codes, it was instead insisted that the first three symbols be fixed and the others be paired so that the spacing between two valid symbols was always the same, so a slice of two symbols in width would be dramatically more specific while retaining most of the benefits of the single wide symbol slice shown above.
[00397] There are several benefits to this variation. For example, the idea of "symbol length slices" is appropriate for real-time execution: large numbers of data points are consumed and converted to fewer points that can later be used to find a package, find its frequency , and decode your information - which is the primary purpose of slices in the first place.
[00398] In this case, the packet length was 250 ms (as opposed to Protocol 2, which was ~ 500 ms). Longer packages imply longer symbols, which puts more energy into each symbol, so they are easier to decode. In 250 ms, each symbol was 120 (chips per symbol) * 920 (samples per chip) = 110,400 samples per symbol. In Protocol 2, the number was 220,800 samples per symbol (in both cases, a nominal number of samples, the exact number of samples as transmitted could be 1%, 5% or even 10% higher or lower than the nominal). If it is assumed that an offset of +/- 1% of the nominal frequency range can be used, say 1000 frequency accumulators. For each slice, 220,800 samples can be converted into a slice that has 1000 x 4 data points. For greater accuracy, the top 3 or 4 peaks could be saved for each slice, increasing the saved information from 4000 points to, say, 8000 points. In spite of everything, 220,000 samples are converted to 8000 points if that, a very significant compression rate.
[00399] Second, of course, by eliminating 98% of the noise from the final analysis, the signal and frequency detection can be improved by ~ 6 dB, which is a significant benefit. Additional variations - such as slices of two symbols wide with known separations between these two symbols, could generate additional benefits.
[00400] Third, this variation is to produce a spectrum pattern that clearly indicates that an artificial signal - and not random noise - is present. This would allow, when a single packet produces enough information that it can be determined a signal is there, but not enough to decode it precisely, to find and then combine successive packets that carry the same information, and combine these packets at the slice level . From a practical perspective, combining two packages, each representing five million samples using correlation between the two data sets, would require a very large number of multiplications and additions and would probably not work, as it would be comparing two signals each dominated by noise . On the other hand, the slicing process eliminates 98% of the noise in each slice, and comparing 50 slices from one package to 50 slices from another package would generate a very good chance of aligning them properly with the minimum computation required.
[00401] Fourth, symbol length slices can be useful in adjusting for variations in the transmission clock that occur during packet transmission (fluctuation). When adjusting for fluctuation, the symbol length slice needs a clock that is stable for only the symbol length time. As long as the fluctuation over the entire package does not exceed 2 ps (in this example), the symbols retain their orthogonality. RESULTS OF EXAMPLE DATA OF THE THIRD DEFINITION OF PICO PROTOCOL
[00402] The algorithm used to analyze the data in Protocol 3 is a variation of the one previously described. The biggest difference is the heavy reliance on 1.5 * symbol length slices to find the frequency. In this solution shown to produce strong results, this algorithm (here referred to as Protocol Symbol Slicer 3, or P3SS) is used in a raw frequency mode to quickly scan the frequency for the signal, taking advantage of its broad spectrum, as well as behaved. Then, a fine search using P3SS is used to find the best guess frequency. In high-noise environments, this proposal is superior to using the combined frame-length slice proposal due to the elimination of additional noise (from 75% noise elimination to 98% noise elimination).
[00403] Note that after the symbol slices are created (combined of 240 slices) only the index and peak values of the two upper peaks (at least 35 feet apart) are maintained. These are added to the other two higher magnitudes for each slice of symbol length (or 1.5 * symbolLength) for this frequency. The sum of these two higher magnitudes for each slice becomes this frequency contribution to the "spectrum". All other information - all the noise that appears in the other 90 feet of sampled and resolved data - is discarded. The spectrum resulting from the gross frequency survey at a distance of 228.6 mm (9 inches) from the detector is shown in Figure 100.
[00404] Figure 100 shows a graph of the gross frequency spectrum for the sensor emulator 228.6 mm (9 inches) from the detector. The geometric axis x of this graph represents, in the center, a nominal number of samples per slice of 920. At X = 0, there are 919 samples per slice; at X = 200, there are 921 samples per slice. The resolution shown is 0.01 samples per slice. Thus, the highest transmission frequency is on the left. The peak is clearly located at 112, which means 919 + (112-1) * 0.01 = 920.11 samples per slice.
[00405] At this point, the data frame has been trimmed to include only the package and 3 additional symbols, one and a half on each side of the presumed package location. This eliminates more noise from subsequent analyzes.
[00406] Using this new value as a central frequency and a resolution of 0.002 sample per slice, the P3SS analysis was performed again. The resulting fine spectrum is shown in Figure 101.
[00407] Figure 101 shows a graph of the fine frequency spectrum for the sensor emulator 228.6 mm (9 inches) from the detector. From the fine spectrum, it can be seen that the peak was found at 6 units and that the final length was 920,106 samples per slice. Note that the finer resolution has been extended to two rough points on each side of the center frequency.
[00408] Using this as the final frequency, the combined total packet length slice was used to find the exact record. Figure 102 shows the combined slice using the center frequency found using P3SS. For example, shown in Figure 102 are the key outputs for the intake sensor at a distance of 228.6 mm (9 inches) from the receiver. Figure 102 shows a graph of the combined frame length slice of the detector at 228.6 mm (9 inches) from the source. In Figure 102, the matching template is shown at the highest peaks (blue lines) 2400, while the combined slice data is shown at the slightly shorter peaks (red lines) 2410. Note that these have opposite parity: this information is used to adjust the parity of the incoming data to match the template.
[00409] The template is correlated with the combined slice, resulting in the "bestSums" graph shown in Figure 103. Figure 103 is a graph showing BestSums using data gathered 228.6 mm (9 inches) from the source.
[00410] Using this registration index and frequency after the second P3SS, the symbols were calculated and the final package shown in Figure 104. Figure 104 is a graph showing the symbols of the package and forces using data gathered at 228.6 mm (9 inches) from the source.
[00411] The same process was used at 609.6 mm (24 inches) with the following results:
[00412] Figure 105 is a graph showing the raw frequency spectrum for the sensor emulator 609.6 mm (24 inches) from the detector.
[00413] Using the raw frequency of 920.11 as the center frequency, P3SS2 (a second variation of P3SS with the adjusted raw frequency) was performed and found the finer spectrum as shown in Figure 106. Figure 106 shows the spectrum of P3SS2 fine frequency for sensor emulator 609.6 mm (24 inches) from the detector.
[00414] At this time P3SS2 was out by slice length of 0.004 sample points per slice, and the decoding was inaccurate. Repeating the fine scan with the full frame slice technique produced the following spectrum as shown in Figure 107. Figure 107 shows the thin full frame frequency spectrum for the sensor emulator at 609.6 mm (24 inches) from the detector.
[00415] The full frame spectrum provided a better estimate of the best slice length, 920,104, and this led to a successful decoding of the packet. The intermediate sets are shown in Figure 108. Figure 108 shows a graph of the best combined total frame slice together with a best fit template for the 609.6 mm (24 inch) signal from the source. Again, the highest peaks represent the template and the shortest peaks are from the total frame slice.
[00416] Figure 109 is a graph showing the result of bestSums (result of template convolution with combined slice) for data gathered 609.6 mm (24 inches) from the source. Using the index in Figure 109, the symbols were successfully decoded. The resulting symbols and the convolution sums that went with them are shown in Figure 110.
[00417] Figure 110 is a graph showing the symbol and package result values for data gathered 609.6 mm (24 inches) from the source. These results indicate the utility of peak distortion communication protocol for ingestion sensor communication.
[00418] Figure 111 is a graph showing BestSums using data gathered at 609.6 mm (24 inches) from the source. EXEMPLARY RECEPTORS USING IMPULSE PROTOCOLS
[00419] Having described the generation and transmission of the "sparse impulses" impulse function, the description now turns to various receiver circuits to receive and decode the signals transmitted by the pulse inductor drive circuit 720. Consequently, Figure 47 illustrates a voltage mode receiver 900 for detecting an electromagnetic field generated by an ingestible identifier, in accordance with an aspect of the present description. The voltage mode receiver 900 comprises a resonant circuit 902, a low noise amplifier 908 (LNA), and a receiver processor 910 comprising circuits and components for processing the received and encoded electromagnetic signal transmitted from the ingestible identifier. The resonant circuit 902 comprises a receiving inductor antenna 904 and a tuning capacitor 906 for resonating at operating frequency f0. The receiving inductor 904 receives the electromagnetic signal in the form factor of a path with the inductor 904.
[00420] It will be appreciated that in Figures 44-46, the horizontal axis may not necessarily represent time, since the signal can be stretched or compressed into a fixed number of data points. If the signal is at nominal frequency, then the corresponding data points will correspond in time, but the units would probably not be in microseconds, but instead the unit would be scaled for whatever the chip's duration, which could vary depending on the Implementation.
[00421] The impulse response of the receiving inductor 904 is shown graphically in Figure 48. The signal received over frequency (f) appears through capacitor 906 in the form of voltage. The 922 response curve has the highest amplitude or energy at operating frequency f0. Referring back to Figure 47, the voltage signal v through the tuning capacitor 906 is applied to the input of LNA 908. The output of LNA 908 is applied to the receiver processor 910, which processes and decodes the received signal to reproduce the 912 data transmitted by the ingestible identifier.
[00422] Figure 49 illustrates a voltage mode receiver 930 for detecting an electromagnetic field generated by an ingestible identifier, in accordance with an aspect of the present description. The receiver 930 comprises a resonant circuit 932, a low noise amplifier 938 (LNA), a narrow band resonator or crystal filter 944, and a receiver processor 940 comprising components to process the received encoded electromagnetic signal transmitted by the ingestible identifier . The resonant circuit 932 comprises an inductor antenna 934 and a tuning capacitor 936 for resonating at operating frequency f0. Inductor 934 receives the electromagnetic signal in the form of a path with inductor 934.
[00423] The impulse response of the receiving inductor 934 is shown graphically in Figure 49. The signal received over frequency (f) appears through capacitor 936 as a voltage. The response curve has the highest amplitude or energy at operating frequency f0. The voltage signal v through tuning capacitor 936 is applied to LNA 938. The output from LNA 938 is applied to the resonator or crystal filter 944, which is coupled to the receiver processor 940. The receiver processor 940 processes and decodes the signal received to reproduce the data 942 transmitted by the ingestible identifier.
[00424] The 944 resonator or crystal filter may comprise one or more resonators or crystals coupled to adjust the selectivity of the 944 filter. Other types of filters that can be employed include, without limitation, grouped inductor / capacitor (LC) filters , flat filters, coaxial filters, cavity filters, dielectric filters, electroacoustic filters, and / or waveguide filters.
[00425] Receiver processors 910, 940 may comprise analog or digital bandpass filters to filter incoming pulses. The voltage of each pulse can be integrated over time in case the pulses are too short. Transmission frequencies can occur in frequencies in the range of ~ 12.5 kHz to ~ 20 kHz or greater than ~ 24 kHz and as high as ~ 10 MHz, for example. Although the pulses are not deterministic, they repeat over 128 pulses at a repetition rate of ~ 6 kHz. Battery readiness is random and battery impedance (Z) and voltage (VBAT) can fluctuate. The pulse width and repetition rate can be adjusted based on the current condition of the battery. These types of protocols can be adapted to circuits of the Internet of Things type.
[00426] Receiver processors 910, 940 discussed in connection with Figures 47 and 49 are configured to process the encoded electromagnetic analog signal transmitted by the ingestible identifier using a sparse impulse template and convolution technique to identify the transmission frequency. In one aspect, receiver processors 910, 940 may comprise an analog to digital converter (ADC) at the initial interface for receiving sparse analog pulses from amplifier circuits 908, 938. The ADC digitizes the series of sparse pulses received in the form of voltages analog signals and output a digital number that represents the voltage amplitude. The digital numbers issued from the ADC are then applied to a processor, such as, for example, a digital signal processor (DSP) optimized to determine the transmission frequency of the sparse pulse signal and decode sparse pulse signal to extract or reproduce the data 912, 942 transmitted by the ingestible identifier. The DSP is well suited for measuring, filtering, and / or continuous compression of analog signals from sparse pulses and executing algorithms. Alternatively, a general purpose microprocessor can also be configured to run the digital signal processing algorithms successfully. After all, dedicated DSPs usually have better power efficiency so they are more suitable for portable devices, such as mobile phones due to power consumption restrictions. DSPs often use special memory architectures that are capable of fetching multiple data and / or instructions at the same time. Although general purpose DSP and microprocessors can be employed, dedicated circuits or reconfigurable circuits such as PLDs, PGA, FPGA, ASICs, and other circuits can be employed alone or in conjunction with general purpose DSPs and microprocessors to perform receiver functions .
[00427] In addition to the voltage mode receiver circuits 900, 930 described in connection with Figures 47-49, multiple other receiver circuits can be employed to receive and decode the electromagnetic analog signal transmitted by the ingestible identifier. Figure 50 illustrates a current mode receiver 950, in accordance with an aspect of the present description. The current mode receiver 950 comprises a reception inductor 952 coupled to a transimpedance amplifier 954 (TIA), which provides low output impedance. The TIA 954 is coupled to an amplifier 956 and its output is coupled to a receiver processor 958, similar to receiver processors 910, 940 (Figures 47, 49). The TIA 954 is beneficial for preserving the shape of the received pulse, so that the impedance of the inductor fluctuates or is coupled through the TIA 954 and thereafter the pulse can be reconstructed from the output of the TIA 954 and is independent of any parasitic capacitance of the TIA 954.
[00428] Figure 51 illustrates another 960 receiver circuit, in accordance with an aspect of the present description. The receiver 960 comprises a reception inductor 962 coupled to a first amplifier 964. The output of the first amplifier 964 is coupled to a second amplifier 966. The output of the second amplifier 966 is coupled to a receiver processor 967. In the example illustrated in Figure 51, the receiver processor 967 comprises an ADC 968 and a DSP 969 for determining the transmission frequency of the sparse pulse signal and decoding the encoded sparse pulse signal to extract or reproduce the data transmitted by the ingestible identifier. The DSP can also be implemented to filter the sparse pulse analog signal and execute various algorithms.
[00429] Figure 52 illustrates a receiver configuration 970 comprising reception inductors 972, 974, 976 orthogonally spaced with respect to each other and corresponding receivers 978, 980, 982, in accordance with an aspect of the present description. Reception inductors 972, 974, 976 have a total elongated shape factor. The receiving inductors 972, 974, 976 and the corresponding receivers 978, 980, 982 are arranged along geometric axes X, Y, Z to mitigate the dependence on the orientation of the transmitter. The outputs of receivers 978, 980, 982 are coupled to a multiplexer 984. The output of multiplexer 984 is coupled to a receiver processor 986 comprising an ADC 988 and a DSP 989.
[00430] Figure 53 illustrates a receiver configuration 990 comprising orthogonally spaced receiving inductors 992, 994, 996 and corresponding receivers 998, 1000, 1002, in accordance with an aspect of the present description. Two of the receiving inductors 992, 994 have a total elongated shape factor and one of the receiving inductors 996 has a total flat shape factor. The reception inductors 992, 994, 996 and the corresponding receivers 998, 1000, 1002 are arranged along geometric axes X, Y, Z to mitigate the dependence on the orientation of the transmitter. The outputs of receivers 998, 1000, 1002 are coupled to a multiplexer 1004. The output of multiplexer 1004 is coupled to a receiver processor 1006 comprising an ADC 1008 and a DSP 1009.
[00431] Figure 54 illustrates a 1010 receiver configuration comprising multiple L1-Ln reception inductors and multiple RXi-RXn receiver amplifiers, in accordance with an aspect of the present description. The L1-Ln receiver inductors are coupled to the corresponding RXi-RXn receiver inputs. The outputs of the RXi-RXn receiver amplifiers are coupled to a multiplexer 1012. The output of multiplexer 1012 is coupled to a receiver processor 1014. As previously discussed, the receiver processor 1014 comprises an ADC 1016 and a DSP 1018 coupled to the ADC 1016. The multiple L1- Ln reception inductors and corresponding corresponding RXi-RXn receiver amplifiers improve the signal-to-noise ratio (SNR), orientation dependency, among others.
[00432] Figure 55 illustrates a receiver circuit 1100, in accordance with an aspect of the present description. Receiver circuit 1100 shown in Figure 55 comprises an analog input interface circuit 1101 coupled to a receiver processor circuit 1103. Analog input interface circuit 1101 comprises a receiver inductor 1108, 1110, 1112 coupled to an amplifier receiver 1102, 1104, 1106. The signals transmitted by the impulse drive circuit, such as the impulse drive circuit 720 shown in Figures 38 and 39 or the impulse drive circuit 726 shown in Figure 43, are received by the inductors receiver 1108, 1110, 1112 arranged along geometric axes X, Y, Z to mitigate the dependence of the transmitter orientation and amplified by the corresponding receiver amplifiers 1102, 1104, 1106. As shown in Figure 55, three receiver inductors 1108 , 1110, 1112 are coupled to three corresponding receiver amplifiers 1102, 1104, 1106. The outputs of the three receiver amplifiers 1102, 1104, 1106 are multiplexed by a multiplexer 1120. In several respects, the receiver processor 1100 can receive signals from one receiver inductor 1108, two receiver inductors 1108, 1110, or more than three receiver inductors 1108, 1110, 1112 depending on the details system implementation.
[00433] The 1120 multiplexer is electrically coupled to one or more bandpass filters. As shown in Figure 55, the multiplexer 1120 is electrically coupled to a high band pass filter 1130 and a low band pass filter 1140 to filter the transmitted frequencies used to transmit the pulse function. Bandpass filters and additional amplifiers can be coupled to the 1120 multiplexer to cover the frequency bands between those recited here. The high and low frequency signal chains provide a programmable gain to cover the desired level or range. In this specific aspect, the high bandpass filter 1130 passes frequencies in the ~ 500 KHz to ~ 1500 KHz band while filtering out-of-band frequency noise. This high frequency band may vary and may include, for example, a range of ~ 800 KHz to ~ 1200 KHz, and in some respects frequencies of ~ 1000 KHz. Pass-through frequencies are then amplified by an 1132 amplifier before being converted into a digital signal by an 1134 analog to digital converter (ADC) for insertion into a 1180 high power processor (shown as a DSP) which is electrically coupled not high frequency signal chain.
[00434] A low bandpass filter 1140 is shown to pass lower frequencies in the range of ~ 50 KHz to ~ 150 KHz while filtering out-of-band frequencies. The frequency band may vary, and may include, for example, frequencies in the range of ~ 80 KHz to ~ 120 KHz, and in some respects frequencies of ~ 100 KHz. Passing frequency signals are amplified by an 1142 amplifier. Also shown is an accelerometer 1150 electrically coupled to the second multiplexer 1160. A multiplexer 1160 multiplexes the accelerometer signals with the amplified signals from the 1142 amplifier. The multiplexed signals are then converted into signals by an ADC 1164 which is also electrically coupled to the 1170 low power processor.
[00435] In one aspect, optionally, an 1150 accelerometer can be multiplexed with the 1142 amplifier output by an 1160 multiplexer. A digital accelerometer (such as one manufactured by Analog Devices), can be implemented in place of the 1150 accelerometer. Several advantages can be achieved using a digital accelerometer. For example, as the signals that the digital accelerometer would produce signals already in digital format, the digital accelerometer 1150 could bypass the ADC 1164 and electrically connect to a low power 1170 microcontroller, in which case the 1160 multiplexer would no longer be required. Also, the digital signal can be configured to turn on itself when detecting movement, additionally conserving energy. In addition, a continuous step count can be implemented. The digital accelerometer can include a FIFO buffer to help control the flow of data sent to the 1170 low power processor. For example, data can be stored in the FIFO until full, at which time the processor can be triggered to wake up from an idle state and receive the data.
[00436] The low power processor 1170 can be, for example, an MSP430 microcontroller from Texas Instruments. The low power processor 1170 and receiver 1100 maintain an idle state, which as previously stated, requires minimal current consumption, for example, ~ 10 pA or less, or ~ 1 pA or less.
[00437] The high power processor 1180 can be, for example, a digital signal processor VC5509 from Texas Instruments. The 1180 high-power processor performs signal processing actions during the active state. These actions, as previously stated, require greater amounts of current than the idle state, for example, currents of 30 pA or more, such as 50 pA or more, and may include, for example, actions such as scanning for conductively transmitted signals , processing conductively transmitted signals when received, obtaining and / or processing physiological data, etc.
[00438] The 1100 receiver can include a hardware accelerator component to process data signals. The hardware accelerator component can be implemented instead of, for example, a DSP. Being a more specialized computing unit, it performs aspects of the signal processing algorithm with fewer transistors (lower cost and power) compared to the DSP of more general use. Hardware blocks can be used to "speed up" the performance of important specific function (s). Some architectures for hardware accelerators can be "programmable" using microcode or very long instruction word assembly (VLIW) language. During use, its functions can be accessed by calls to function libraries.
[00439] The hardware accelerator component (HWA) comprises an HWA input block to receive an input signal that must be processed and instructions to process the input signal; and, an HWA processing block for processing the input signal according to instructions received and for generating a resulting output signal. The resulting output signal can be transmitted as needed via an HWA output block.
[00440] Also shown in Figure 55 is an instant memory 1190 electrically coupled to the high power processor 1180. In one aspect, the instant memory 1190 can be electrically coupled to the low power processor 1170, which can provide better power efficiency .
[00441] A wireless communication element 1195 is shown electrically coupled to the high power processor 1180 and may include, for example, a BLUETOOTH ™ wireless communication transceiver. In one aspect, the wireless communication element 1195 is electrically coupled to the high power processor 1180. In another aspect, the wireless communication element 1195 is electrically coupled to the high power processor 1180 and the low power processor 1170. More furthermore, the wireless communication element 1195 can be implemented to have its own power supply, so that it can be turned on and off independently of other components of the receiver, for example, by a microprocessor.
[00442] It should be appreciated that any patent, publication, or other disclosure material, in whole or in part, that is said to be incorporated herein by reference is incorporated here only insofar as the incorporated material does not conflict with existing definitions, statements , or other description material presented in this description. As such, and as necessary, the description as explicitly set forth herein replaces any conflicting material incorporated herein by reference. Any material, or its portion, that is said to be incorporated herein by reference, but which conflicts with existing definitions, statements, or other description material presented herein will only be incorporated to the extent that no conflict arises between the incorporated material and the material existing description.
[00443] Although several details have been presented in the description above, it will be appreciated that the various aspects of perception and electromagnetic detection of ingestible event markers can be practiced without these specific details. For example, for the sake of clarity selected aspects were shown in the form of a block diagram rather than in detail. Some portions of the detailed descriptions provided here can be presented in terms of instructions that operate on stored data that are stored in a computer memory. Such descriptions and representations are used by those skilled in the art to describe and convey the substance of their work to others skilled in the art. In general, an algorithm refers to a sequence of self-consistent steps that leads to a desired result, where a "step" refers to a manipulation of physical quantities which may, although not necessarily, take the form of electrical signals or magnetic capable of being stored, transferred, combined, compared, and otherwise manipulated. It is in common use to refer to these signs as bits, values, elements, symbols, characters, terms, numbers or the like. These and similar terms can be associated with the appropriate physical quantities and are merely convenient labels applied to these quantities.
[00444] Unless specifically stated otherwise as apparent from the above discussion, it is appreciated that, throughout the above description, discussions using terms such as "process" or "compute" or "calculate" or "determine" or "display" or similar, refers to the action and processes of a computer system, or similar electronic computing device, that manipulates and transforms data represented as physical (electronic) quantities within the computer system's records and memories into other data similarly represented as physical quantities within computer system memories or records or other such information storage, transmission or display devices.
[00445] It is worth noting that any reference to "an aspect", "the aspect", "an aspect", or "the aspect" means that a specific aspect, structure, or feature described in connection with the aspect is included in at least one aspect. Thus, appearances of the phrases "in one aspect", "in aspect", "in one aspect", "in aspect" in various places across all specifications are not necessarily all referring to the same aspect. Furthermore, specific aspects, structures or characteristics can be combined in any suitable way in one or more aspects.
[00446] Although several aspects have been described here, many modifications, variations, substitutions, changes and equivalents to these aspects can be implemented and will occur to those skilled in the art. Also, where materials are described for certain components, other materials can be used. It should, therefore, be understood that the above description and the appended claims are intended to cover all such modifications and variations that fall within the scope of the described aspects. The following claims are intended to cover all such modifications and variations.
[00447] Some or all of the various aspects described here can generally comprise technologies for electromagnetic perception and detection of ingestible identifiers according to the technologies described here. In a general sense, those skilled in the art will recognize that the various aspects described here which can be implemented, individually and / or collectively, by a wide range of hardware, software, firmware, or any combination thereof can be seen as being composed of various types of "electrical circuit". Consequently, as used herein "electrical circuit" includes, but is not limited to, an electrical circuit that has at least one discrete electrical circuit, an electrical circuit that has at least one integrated circuit, an electrical circuit that has at least one integrated circuit application-specific, an electrical circuit that forms a general-purpose computing device configured by a computer program (for example, a general-purpose computer configured by a computer program which at least partially performs processes and / or devices described herein , or a microprocessor configured by a computer program which at least partially executes processes and / or devices described herein), an electrical circuit that forms a memory device (for example, random access memory forms), and / or a electrical circuit that forms a communications device (for example, a modem, communications switch, or optical-electrical equipment O). Those skilled in the art will recognize that the subject described here can be implemented in an analog or digital mode or some combination thereof.
[00448] The detailed description above presented various aspects of the devices and / or processes through the use of block diagrams, flowcharts and / or examples. To the extent that such block diagrams, flowcharts, and / or examples contain one or more functions and / or operations, it will be understood by those skilled in the art that each function and / or operation within such block diagrams, flowcharts, or examples they can be implemented, individually and / or collectively, by a wide range of hardware, software, firmware, or virtually any combination thereof. In one aspect, several portions of the subject described here can be implemented through Application Specific Integrated Circuits (ASICs), Field Programmable Port Networks (FPGAs), digital signal processors (DSPs), or other integrated formats.
[00449] Those skilled in the art will recognize, however, that some aspects of the aspects described here, in whole or in part, can be equivalently implemented in an integrated circuit, such as one or more computer programs that run on one or more computers ( for example, as one or more programs that run on one or more computer systems), as one or more programs that run on one or more processors (for example, as one or more programs that run on one or more microprocessors), as firmware, or as virtually any combination thereof, and that designing the circuit and / or writing the code for the software and / or firmware would be well within the ability of someone skilled in the art in light of this description. In addition, those skilled in the art will appreciate that the mechanisms of the subject described here are capable of being distributed as a program product in a variety of ways, and that an illustrative aspect of the subject described here applies regardless of the specific type of support medium. signal used to actually execute the distribution. Examples of a signal support medium include, but are not limited to, the following: a recordable type medium such as a floppy disk, a hard disk drive, a Compact Disc (CD), a Digital Video Disc (DVD) ), digital tape, computer memory, etc .; and a transmission type medium such as a digital and / or analog communication medium (for example, a fiber optic cable, a waveguide, a wired communications connection, a wireless communication connection (for example, transmitter, receiver, transmission logic, reception logic, etc.).
[00450] Someone skilled in the art will recognize that the components described here (for example, operations), devices, objects, and the accompanying discussion are used as examples for the sake of conceptual clarity and that several configuration changes are contemplated. Consequently, as used here, specific examples presented and the accompanying discussion are intended to be representative of their more general classes. In general, the use of any specific example is intended to be representative of its class, and the non-inclusion of specific components (eg, operations), devices, and objects should not be taken as limiting.
[00451] With respect to the use of substantially any plural and / or singular terms here, those skilled in the art can translate from the plural to the singular and / or from the singular to the plural as appropriate to the context and / or application. The various singular / plural permutations are not expressly presented here for the sake of clarity.
[00452] The subject described here, sometimes, illustrates different components contained in, or connected with different other components. It must be understood that such architectures presented are merely exemplary, and that in fact many other architectures can be implemented which achieve the same functionality. In a conceptual sense, any arrangement of components to achieve the same functionality is effectively "associated", so that the desired functionality is achieved. With this, any two components combined here to achieve a specific functionality can be seen as "associated" with each other so that the desired functionality is achieved, regardless of intermediary architectures or components. Likewise, any two components so associated can also be seen as "operably connected", or "operably coupled", to each other to achieve the desired functionality, and any two components capable of being so associated can also be seen as " operably attachable "to each other to achieve the desired functionality. Specific examples of operably dockable include, but are not limited to, physically compatible and / or physically interactive, and / or wireless interactive components, and / or wireless interactive components, and / or logically interactive, and / or logically interoperable components.
[00453] Some aspects can be described using the expression "coupled" and "connected" together with their derivatives. It should be understood that these terms are not intended to be synonymous with each other. For example, some aspects can be described using the term "connected" to indicate that two or more elements are in direct physical or electrical contact with each other. In another example, some aspects can be described using the term "coupled" to indicate that two or more elements are in direct physical or electrical contact. The term "coupled", however, can also mean that two or more elements are not in direct contact with each other, but, however, still cooperate or interact with each other.
[00454] In some cases, one or more components may be referred to here as "configured for", "configurable for", "operable / operative for", "adapted / adaptable", "capable of", "conformable / conformed to" , etc. Those skilled in the art will recognize that "configured for" can generally encompass active state components and / or inactive state components and / or standby state components, unless the context requires otherwise.
[00455] Although specific aspects of the present subject described here have been shown and described, it will be apparent to those versed in the technique that, based on the teachings here, changes and modifications can be made without departing from the subject described here and its broader aspects therefore, the appended claims must cover within its scope all such changes and modifications as they are within the true spirit and scope of the subject described herein. It will be understood by those skilled in the art that, in general, terms used herein, and especially in the appended claims (for example, bodies of the appended claims) are generally intended as "open" terms (for example, the term "including" should be interpreted as "including, but not limited to", the term "having" should be interpreted as "having at least", the term "includes" should be interpreted as "includes, but is not limited to", etc.). It will also be understood by those skilled in the art that if a specific number of an introduced claim recitation is intended, that intention will be explicitly recited in the claim, and in the absence of such a recitation no such intention is present. For example, as an aid to understanding, the following appended claims may contain the use of the introductory phrases "at least one" and "one or more" to enter claim claims. However, the use of such phrases should not be considered to imply that the introduction of a claim recitation by the indefinite articles "one" or "one" limits any specific claim that contains such an introduced claim recital to claims containing only such recitation, even when the same claim includes the introductory phrases "one or more" or "at least one" and indefinite articles such as "one" or "one" (for example, "one" and / or "one" should typically be interpreted mean "at least one" or "one or more"); the same is true for using defined articles used to enter claims claims.
[00456] Furthermore, even if a specific number of an entered claim recitation is explicitly recited, those skilled in the art will recognize that such a recitation must typically be interpreted to mean at least the recited number (for example, a simple recitation of "two recitations" ", without other modifiers, typically means at least two recitations, or two or more recitations). In addition, in those cases where a convention analogous to "at least one of A, B, and C, etc.," is used, in general such a construction is intended in the sense that someone skilled in the art would understand the invention (for example, " a system that has at least one of A, B, and C ”would include, but would not be limited to, systems that have A alone, B alone, C alone, A and B together, A and C together, B and C together, and / or A, B, and C together, etc.). In those cases where a convention analogous to "at least one of A, B, or C, etc." is used, in general such construction is intended in the sense that someone skilled in the art would understand the convention (for example, "a system that has at least one of A, B, or C" would include, but would not be limited to systems that have A alone, B alone, C alone, A and B together, A and C together, B and C together, and / or A, B, and C together, etc.). It will also be understood by those skilled in the art that typically a disjunctive word and / or phrase that presents two or more alternative terms, whether in the description and claims or drawings, must be understood to include the possibilities of including one of the terms, any of the terms, or both terms, unless the context dictates otherwise. For example, the phrase "A or B" will typically be understood to include the possibilities of "A" or "B" or "A and B".
[00457] With respect to the attached claims, those skilled in the art will appreciate that operations recited therein can generally be performed in any order. Also, although several operational flows are presented in a sequence (s), it must be understood that the various operations can be performed in other orders than those which are illustrated, or can be performed concurrently. Examples of such alternative orderings may include overlapping, interleaving, interruption, reordering, incremental, preparatory, supplementary, simultaneous, reverse, or other variant orderings, unless the context dictates otherwise. Furthermore, terms such as "responsive to", "relative to", or other adjectives from the past tense are generally not intended to exclude such variants, unless the context dictates otherwise.
[00458] In certain cases, the use of a system or method can occur in a territory even if the components are located outside the territory. For example, in a distributed computing context, the use of a distributed computing system can occur in a territory even though parts of the system may be located outside the territory (for example, relay, server, processor, signal support medium, transmitting computer, receiving computer, etc. located outside the territory).
[00459] A sale of a system or method can likewise occur in a territory even if the components of the system or method are located and / or used outside the territory. Furthermore, the implementation of at least part of a system to execute a method in one territory does not prevent the use of the system in another territory.
[00460] Although several aspects have been described here, many modifications, variations, substitutions, changes, and equivalents to these aspects can be implemented and will occur to those skilled in the art. Also, where materials are described for certain components, other materials can be used. It should, therefore, be understood that the above description and the appended claims are intended to cover all such modifications and variations that fall within the scope of the described aspects. The following claims are intended to cover all such modifications and variations.
[00461] In summary, numerous benefits have been described which result from employing the concepts described here. The above description of one or more aspects has been presented for purposes of illustration and description. This is not intended to be exhaustive or to limit to the precise form described. Modifications or variations are possible in light of the above teachings. The one or more aspects were chosen and described in order to illustrate the principles and practical application to thereby allow someone skilled in the art to use the various aspects and with various modifications as they are suitable for the specific use contemplated. It is intended that the claims submitted with this define the general scope.
[00462] Several aspects of the subject described here are presented in the following numbered clauses: 1. An electronic device comprising: a control device; a drive circuit coupled to the control device, the drive circuit configured to change the conductance; a partial power source coupled to the control device, the partial power source is configured to provide a voltage potential difference for the control device and the drive circuit as a result of the partial power source being in contact with a fluid conductive, the partial energy source comprising: a first material electrically coupled to the control device; and a second material electrically coupled to the control device and electrically isolated from the first material; an inductor coupled to the drive circuit, where the drive circuit is configured to develop a current through the inductor, and where a magnitude of the current developed through the inductor is varied to produce a coded signal that is remotely detectable by a receiver. 2. The electronic device of clause 1, wherein the drive circuit comprises a single-ended drive circuit. 3. The electronic device of clause 1, in which the drive circuit comprises a push-pull H bridge drive circuit. 4. The electronic device of clause 1, in which the drive circuit comprises: cross coupled transistors; and a capacitor coupled between the drains of the cross coupled transistors; where the inductor is coupled between the drains of the cross coupled transistors. 5. The electronic device of clause 1, further comprising: a battery voltage doubling circuit; a pulse generator circuit coupled to the battery voltage doubling circuit; and an inductor discharge circuit coupled to the pulse generator circuit. 6. The electronic device of clause 5, in which the battery voltage duplicating circuit comprises: a switched capacitor stage comprising first and second switched capacitors, in which the switched capacitor stage receives an input voltage and emits a voltage of output that has a magnitude of twice the input voltage; and a clock stage; where the clock stage receives a pulse train and produces opposite phase clock pulses, where the opposite phase clock pulses cause the first and second capacitors to alternately charge to a voltage equal to twice the input voltage . 7. The electronic circuit of clause 5, in which the pulse generator circuit comprises: a first and a second trigger circuit; an RC timing circuit comprising a resistor R and a capacitor C for adjusting a time constant delay T at the input of the second delayed trigger circuit; an inverter coupled to the output of the first non-delayed trip circuit; and a logic gate having a first input coupled to an inverter output, a second input coupled to an output of the second trip circuit, and an output coupled to the inductor trip circuit; a first oscillator coupled to the input of the first trip circuit and coupled to the RC timing circuit; and a second oscillator coupled to the inductor trip circuit. 8. The electronic circuit of clause 5, in which the inductor discharge circuit comprises: a capacitor charging circuit; a coupling circuit; and charging and discharging circuits for charging and discharging the inductor. 9. The electronic circuit of clause 1, in which the drive circuit is configured to implement an impulse communication protocol. 10. The electronic device of clause 1, in which the first and second materials are selected to provide the voltage potential difference as a result of the first and second materials being in contact with the conductive fluid. 11. The electronic device of clause 1, which comprises an electronic switch, in which the electronic switch comprises a first and second terminals and a control terminal, and in which the control terminal is operably coupled to the drive circuit, the first terminal is connected to the inductor, and the second terminal is connected to the second material, and where the inductor is connected between the first material and the first terminal of the electronic switch, where the drive circuit is configured to change the conductance of the electronic switch between the first and second materials so that the current is developed through the inductor. 12. The electronic device of clause 1, in which the inductor comprises at least two inductive elements formed on insulating substructures separate from a semiconductor integrated circuit. 13. The electronic device of clause 12, in which the at least two inductive elements are coupled through a path formed between the separate insulating substructures. 14. A receiver circuit, comprising: a resonant circuit; a low noise voltage amplifier coupled to the resonant circuit; and a receiver processor circuit coupled to a low noise voltage amplifier output, the receiver processor configured to receive an analog signal representative of a pulse communication signal, convert the analog signal to a digital signal, and decode the digital signal to reproduce the transmitted data as the pulse communication signal. 15. The receiver of clause 14, further comprising a narrow band resonator coupled between the low noise amplifier and the receiver processor circuit. 16. A receiver circuit, comprising: a receiving inductor; a transimpedance amplifier coupled to the receiving coil; an amplifier coupled to a transimpedance amplifier output; and a receiver processor circuit coupled to an amplifier output, the receiver processor configured to receive an analog signal representative of a pulse communication signal, convert the analog signal to a digital signal, and decode the digital signal to reproduce the transmitted data as the pulse communication signal. 17. The receiver circuit of clause 16, wherein the receiver processor comprises: an analog to digital converter (ADC); and a digital signal processor coupled to an ADC output. 18. The receiver of clause 16, which comprises: at least three reception inductors orthogonally spaced from each other; at least three amplifiers coupled to corresponding orthogonally spaced inductors; a multiplexer to receive the outputs from at least three amplifiers; an analog to digital converter (ADC) coupled to a multiplexer output; and a digital signal processor coupled to an ADC output. 19. The clause 18 receiver, where at least one of the three inductors has a total elongated shape factor. 20. The clause 18 receiver, where at least one of the three inductors has a total flat form factor. 21. The clause 16 receiver, which comprises: a plurality of bandpass filters coupled to the output of the multiplexer, where each bandpass filter is tuned to a different frequency band; a plurality of amplifiers coupled to the corresponding plurality of bandpass filters; a plurality of analog to digital converters (ADCs) that have inputs coupled to outputs of the bandpass filters and that have outputs coupled to the digital signal processor. 22. The receiver of clause 21, still comprising a wireless communication element. 23. The clause 16 receiver, which comprises: a plurality of reception inducers; a plurality of corresponding amplifiers coupled to the plurality of inductors; a multiplexer for receiving the outputs from the plurality of amplifiers; an analog to digital converter (ADC) coupled to a multiplexer output; and a digital signal processor coupled to an ADC output. 24. The receiver of clause 23, in which the plurality of reception inductors is arranged in a circular pattern.

权利要求:
Claims (24)
[0001]
1. Electronic device characterized by the fact that it comprises: a control device (218, 228, 422, 430, 506); a drive circuit (500, 502, 700, 720) coupled to the control device (218, 228, 422, 430, 506), the drive circuit (500, 502, 700, 720) configured to change conductance and comprising : cross coupled transistors; and a capacitor coupled between drains of the cross coupled transistors; a partial power source coupled to the control device (218, 228, 422, 430, 506), where the partial power source is configured to provide a voltage potential difference to the control device (218, 228, 422, 430, 506) and the drive circuit (500, 502, 700, 720) as a result of the partial energy source being in contact with a conductive fluid, the partial energy source comprising: a first material electrically coupled to the control device (218, 228, 422, 430, 506); and a second material electrically coupled to the control device (218, 228, 422, 430, 506) and electrically isolated from the first material; and an inductor coupled to the drive circuit (500, 502, 700, 720), where the drive circuit (500, 502, 700, 720) is configured to develop a current through the inductor, where the inductor is coupled between the drains of the cross coupled transistors, and in which a magnitude of the current developed through the inductor is varied to produce an encoded signal that is remotely detectable by a receiver.
[0002]
2. Electronic device according to claim 1, characterized by the fact that the drive circuit (500, 502, 700, 720) comprises a single-ended drive circuit (500).
[0003]
3. Electronic device according to claim 1, characterized by the fact that the drive circuit (500, 502, 700, 720) comprises a push-pull H bridge drive circuit.
[0004]
4. Electronic device, according to claim 1, characterized by the fact that the drive circuit (500, 502, 700, 720) still comprises: a voltage doubling circuit (722) coupled to the partial power source; a pulse generating circuit (724) coupled to the voltage doubling circuit (722); and an inductor discharge circuit (726) coupled to the pulse generator circuit (724).
[0005]
5. Electronic device according to claim 4, characterized by the fact that the voltage doubling circuit (722) comprises: a switched capacitor stage (752) comprising first and second switched capacitors, in which the switched capacitor stage (752) receives an input voltage and emits an output voltage that has a magnitude of twice the input voltage; and a clock stage (754); where the clock stage (754) receives a pulse train and produces opposite phase clock pulses, where the opposite phase clock pulses cause the first and second capacitors to alternately charge to a voltage equal to twice the Input Voltage.
[0006]
6. Electronic circuit, according to claim 4, characterized by the fact that the pulse generator circuit comprises: a non-delayed trigger circuit; a delayed trip circuit; an inductor trip circuit; an RC timing circuit comprising a resistor R and a capacitor C for adjusting a time constant delay at the input of the delayed trigger circuit; an inverter coupled to the output of the non-delayed trip circuit; and a logic gate having a first input coupled to an output of the inverter, a second input coupled to an output of the delayed trip circuit, and an output coupled to the inductor trip circuit; a first oscillator coupled to a non-delayed trigger circuit input and coupled to the RC timing circuit; and a second oscillator coupled to the inductor trip circuit.
[0007]
7. Electronic circuit, according to claim 4, characterized by the fact that the inductor discharge circuit (726) comprises: a capacitor charging circuit; a coupling circuit; and charging and discharging circuits for charging and discharging the inductor.
[0008]
8. Electronic circuit, according to claim 1, characterized by the fact that the drive circuit (500, 502, 700, 720) is configured to implement an impulse communication protocol.
[0009]
9. Electronic device, according to claim 1, characterized by the fact that the first and second materials are selected to provide the voltage potential difference as a result of the first and second materials being in contact with the conductive fluid.
[0010]
10. Electronic device, according to claim 1, characterized by the fact that it still comprises an electronic switch, in which the electronic switch comprises a first and second terminals and a control terminal (428, 511), and in which the terminal control unit (428, 511) is operatively coupled to the drive circuit (500, 502, 700, 720), the first terminal is coupled to the inductor, and the second terminal is coupled to the second material, and the inductor is coupled between the first material and the first terminal of the electronic switch, in which the drive circuit (500, 502, 700, 720) is still configured to change the conductance of the electronic switch between the first and second materials so that the current is developed through of the inductor.
[0011]
11. Electronic device according to claim 1, characterized by the fact that the inductor comprises at least two inductive elements formed on insulating substructures separated from a semiconductor integrated circuit (601, 611, 631, 651).
[0012]
12. Electronic device according to claim 11, characterized by the fact that the at least two inductive elements are coupled through a path formed between the separate insulating substructures.
[0013]
13. Electronic device characterized by the fact that it comprises: a control device (218, 228, 422, 430, 506); a drive circuit (500, 502, 700, 720) coupled to the control device (218, 228, 422, 430, 506), the drive circuit (500, 502, 700, 720) configured to change the conductance; a partial power source coupled to the control device (218, 228, 422, 430, 506), where the partial power source is configured to provide a voltage potential difference to the control device (218, 228, 422, 430, 506) and the drive circuit (500, 502, 700, 720) as a result of the partial energy source being in contact with a conductive fluid, the partial energy source comprising: a first material electrically coupled to the control device (218, 228, 422, 430, 506); and a second material electrically coupled to the control device (218, 228, 422, 430, 506) and electrically isolated from the first material; an inductor coupled to the drive circuit (500, 502, 700, 720), in which drive circuit (500, 502, 700, 720) is configured to develop a current through the inductor, and in which a magnitude of the current developed through the inductor is varied to produce an encoded signal that is remotely detectable by a receiver; and an electronic switch, in which the electronic switch comprises first and second terminals and a control terminal (428, 511), and in which the control terminal (428, 511) is operatively coupled to the drive circuit (500, 502, 700, 720), the first terminal is coupled to the inductor, and the second terminal is coupled to the second material, and the inductor is coupled between the first material and the first terminal of the electronic switch, where the drive circuit (500 , 502, 700, 720) is further configured to change the conductance of the electronic switch between the first and second materials so that the current is developed through the inductor.
[0014]
14. Electronic device, according to claim 13, characterized by the fact that it also comprises: a voltage doubling circuit (722) coupled to the partial energy source; a pulse generating circuit (724) coupled to the voltage doubling circuit (722); and an inductor discharge circuit (726) coupled to the pulse generator circuit (724).
[0015]
15. Electronic device according to claim 14, characterized by the fact that the voltage doubling circuit (722) comprises: a switched capacitor stage (752) comprising first and second switched capacitors, in which the switched capacitor stage ( 752) receives an input voltage and emits an output voltage having a magnitude of twice the input voltage; a clock stage (754); where the clock stage (754) receives a pulse train and produces opposite phase clock pulses, where the opposite phase clock pulses cause the first and second capacitors to alternately carry a voltage equal to twice the voltage input.
[0016]
16. Electronic device characterized by the fact that it comprises: a control device (218, 228, 422, 430, 506); a drive circuit (500, 502, 700, 720) coupled to the control device (218, 228, 422, 430, 506), the drive circuit (500, 502, 700, 720) configured to change a conductance; a partial power source coupled to the control device (218, 228, 422, 430, 506), where the partial power source is configured to provide a voltage potential difference for the control device (218, 228, 422 , 430, 506) and the drive circuit (500, 502, 700, 720) as a result of the partial energy source being in contact with a conductive fluid, the partial energy source comprising: a first material electrically coupled to the control (218, 228, 422, 430, 506); and a second material electrically coupled to the control device (218, 228, 422, 430, 506) and electrically insulated from the first material; an inductor coupled to the drive circuit (500, 502, 700, 720), where the drive circuit (500, 502, 700, 720) is configured to develop a current through the inductor, in which a magnitude of the current developed through of the inductor is varied to produce a coded signal that is remotely detectable by a receiver, and in which the inductor comprises at least two inductive elements formed in insulating substructures separate from a semiconductor integrated circuit (601,611,631,651).
[0017]
17. Electronic device according to claim 16, characterized by the fact that the at least two inductive elements are coupled via a surface area formed between the separate insulating substructures.
[0018]
18. Electronic device, according to claim 16, characterized by the fact that it also comprises: a voltage doubling circuit (722) coupled to the partial energy source; a pulse generating circuit (724) coupled to the voltage doubling circuit (722); and an inductor discharge circuit (726) coupled to the pulse generator circuit (724).
[0019]
19. Electronic device according to claim 18, characterized by the fact that the voltage doubling circuit (722) comprises: a switched capacitor stage (752) comprising first and second switched capacitors, in which the switched capacitor stage ( 752) receives an input voltage and emits an output voltage having a magnitude of twice the input voltage; a clock stage (754); where the clock stage (754) receives a pulse train and produces opposite phase clock pulses, where the opposite phase clock pulses cause the first and second capacitors to alternately charge at a voltage equal to twice the Input Voltage.
[0020]
20. Electronic device characterized by the fact that it comprises: a control device (218, 228, 422, 430, 506); a drive circuit (500, 502, 700, 720) coupled to the control device (218, 228, 422, 430, 506), the drive circuit (500, 502, 700, 720) configured to change a conductance; a partial power source coupled to the control device (218, 228, 422, 430, 506), where the partial power source is configured to provide a voltage potential difference for the control device (218, 228, 422 , 430, 506) and the drive circuit (500, 502, 700, 720) as a result of the partial energy source being in contact with a conductive fluid, the partial energy source comprising: a first material electrically coupled to the control (218, 228, 422, 430, 506); and a second material electrically coupled to the control device (218, 228, 422, 430, 506) and electrically insulated from the first material; an inductor coupled to the drive circuit (500, 502, 700, 720), where the drive circuit (500, 502, 700, 720) is configured to develop a current through the inductor, in which a magnitude of the current developed through the inductor is varied to produce an encoded signal that is remotely detectable by a receiver; a voltage doubling circuit (722) coupled to the partial power source; a pulse generating circuit (724) coupled to the voltage doubling circuit (722); and an inductor discharge circuit (726) coupled to the pulse generator circuit (724).
[0021]
21. Electronic device according to claim 20, characterized by the fact that the voltage doubling circuit (722) comprises: a switched capacitor stage (752) comprising first and second switched capacitors, in which the switched capacitor stage ( 752) receives an input voltage and emits an output voltage having a magnitude of twice the input voltage; a clock stage (754); where the clock stage (754) receives a pulse train and produces opposite phase clock pulses, where the opposite phase clock pulses cause the first and second capacitors to alternately charge at a voltage equal to twice the Input Voltage.
[0022]
22. Electronic device, according to claim 20, characterized by the fact that it comprises: a non-delayed trip circuit; a delayed trip circuit; an inductor trip circuit; an RC timing circuit comprising a resistor R and a capacitor C for adjusting a time constant delay at the input of the delayed trigger circuit; an inverter coupled to the output of the non-delayed trip circuit; and a logic gate having a first input coupled to an output of the inverter, a second input coupled to an output of the delayed trip circuit, and an output coupled to the inductor trip circuit; a first oscillator coupled to a non-delayed trigger circuit input and coupled to the RC timing circuit; and a second oscillator coupled to the inductor trip circuit.
[0023]
23. Electronic device according to claim 20, characterized by the fact that the inductor discharge circuit (726) comprises: a capacitor charging circuit; a coupling circuit; and charging and discharging circuits for charging and discharging the inductor.
[0024]
24. Electronic device according to claim 20, characterized by the fact that the inductor comprises at least two inductive elements formed in separate insulating substructures of a semiconductor integrated circuit (601, 611,631, 651).

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JP2022000191A|2022-01-04|

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JP2019213864A|2019-12-19|

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法律状态:
2020-08-25| B09A| Decision: intention to grant [chapter 9.1 patent gazette]|

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2020-10-27| B16A| Patent or certificate of addition of invention granted [chapter 16.1 patent gazette]|Free format text: PRAZO DE VALIDADE: 20 (VINTE) ANOS CONTADOS A PARTIR DE 24/07/2017, OBSERVADAS AS CONDICOES LEGAIS. |

优先权:

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申请号 | 申请日 | 专利标题

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US201662365727P| true| 2016-07-22|2016-07-22|

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US62/365,727|2016-07-22|

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PCT/US2017/043465|WO2018018034A1|2016-07-22|2017-07-24|Electromagnetic sensing and detection of ingestible event markers|

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